Apparatus for transmitting broadcast signals, apparatus for receiving broadcast signals, method for transmitting broadcast signals and method for receiving broadcast signals

ABSTRACT

A method and device for processing broadcast signals are discussed. The method includes receiving the broadcast signals carrying service data, demodulating the broadcast signals by an Orthogonal Frequency Division Multiplexing (OFDM) scheme, MIMO processing data in the broadcast signals based on a rotation value, where the rotation value has zero (0) degree for a modulation order corresponding to equal to or greater than 64 Quadrature Amplitude Modulation (QAM) and a code rate corresponding to at least one of 2/15, 3/15, 4/15, 5/15, 6/15, 7/15, 8/15, 9/15, 10/15, 11/15, 12/15 or 13/15, and the rotation value has zero (0) degree for a modulation order corresponding to Quadrature Phase Shift Keying (QPSK) and a code rate corresponding to at least one of 2/15, 3/15, 4/15 or 5/15, and decoding the data.

CROSS-REFERENCE TO RELATED APPLICATIONS

This Application is a Divisional of U.S. patent application Ser. No.16/376,891 filed on Apr. 5, 2019, which is a Divisional of U.S. patentapplication Ser. No. 16/175,365 filed on Oct. 30, 2018 (now U.S. Pat.No. 10,277,445, issued on Apr. 30, 2019), which is a Continuation ofU.S. patent application Ser. No. 15/877,068 filed on Jan. 22, 2018 (nowU.S. Pat. No. 10,135,659, issued on Nov. 20, 2018), which is aContinuation of U.S. patent application Ser. No. 15/467,134 filed onMar. 23, 2017 (now U.S. Pat. No. 9,906,393, issued on Feb. 27, 2018),which is a Continuation of U.S. patent application Ser. No. 15/060,165filed on Mar. 3, 2016 (now U.S. Pat. No. 9,635,520, issued on Apr. 25,2017), which claims the benefit under 35 U.S.C. § 119(e) to U.S.Provisional Application Nos. 62/206,812 filed on Aug. 18, 2015,62/204,465 filed on Aug. 13, 2015 and 62/130,561 filed on Mar. 9, 2015,where all of these application are hereby expressly incorporated byreference into the present application.

BACKGROUND OF THE INVENTION Field of the Invention

The present invention relates to an apparatus for transmitting broadcastsignals, an apparatus for receiving broadcast signals and methods fortransmitting and receiving broadcast signals.

Discussion of the Related Art

As analog broadcast signal transmission comes to an end, varioustechnologies for transmitting/receiving digital broadcast signals arebeing developed. A digital broadcast signal may include a larger amountof video/audio data than an analog broadcast signal and further includevarious types of additional data in addition to the video/audio data.

That is, a digital broadcast system can provide HD (high definition)images, multi-channel audio and various additional services. However,data transmission efficiency for transmission of large amounts of data,robustness of transmission/reception networks and network flexibility inconsideration of mobile reception equipment need to be improved fordigital broadcast.

SUMMARY OF THE INVENTION

Accordingly, the present invention is directed to an apparatus fortransmitting broadcast signals and an apparatus for receiving broadcastsignals for future broadcast services and methods for transmitting andreceiving broadcast signals for future broadcast services.

An object of the present invention is to provide an apparatus and methodfor transmitting broadcast signals to multiplex data of a broadcasttransmission/reception system providing two or more different broadcastservices in a time domain and transmit the multiplexed data through thesame RF signal bandwidth and an apparatus and method for receivingbroadcast signals corresponding thereto.

Another object of the present invention is to provide an apparatus fortransmitting broadcast signals, an apparatus for receiving broadcastsignals and methods for transmitting and receiving broadcast signals toclassify data corresponding to services by components, transmit datacorresponding to each component as a data pipe, receive and process thedata

Still another object of the present invention is to provide an apparatusfor transmitting broadcast signals, an apparatus for receiving broadcastsignals and methods for transmitting and receiving broadcast signals tosignal signaling information necessary to provide broadcast signals.

To achieve the object and other advantages and in accordance with thepurpose of the invention, as embodied and broadly described herein, amethod for receiving broadcast signals, the method comprises receivingbroadcast signals, demodulating the received broadcast signals by anOFDM (Orthogonal Frequency Division Multiplex) scheme, parsing signalframes from the demodulated broadcast signals, MIMO (Multi Input MultiOutput) processing service data in the parsed signal frames based on arotation matrix with a rotation angle, wherein the value of the rotationangle depends on a modulation order and code rate of the service data,wherein the modulation order is one of QPSK modulation and NUC(non-uniform constellation), demapping the MIMO processed service dataand decoding the demapped service data.

The present invention can process data according to servicecharacteristics to control QoS (Quality of Services) for each service orservice component, thereby providing various broadcast services.

The present invention can achieve transmission flexibility bytransmitting various broadcast services through the same RF signalbandwidth.

The present invention can improve data transmission efficiency andincrease robustness of transmission/reception of broadcast signals usinga MIMO system.

According to the present invention, it is possible to provide broadcastsignal transmission and reception methods and apparatus capable ofreceiving digital broadcast signals without error even with mobilereception equipment or in an indoor environment.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings, which are included to provide a furtherunderstanding of the invention and are incorporated in and constitute apart of this application, illustrate embodiment(s) of the invention andtogether with the description serve to explain the principle of theinvention. In the drawings:

FIG. 1 illustrates a structure of an apparatus for transmittingbroadcast signals for future broadcast services according to anembodiment of the present invention.

FIG. 2 illustrates an input formatting block according to one embodimentof the present invention.

FIG. 3 illustrates an input formatting block according to anotherembodiment of the present invention.

FIG. 4 illustrates an input formatting block according to anotherembodiment of the present invention.

FIG. 5 illustrates a BICM block according to an embodiment of thepresent invention.

FIG. 6 illustrates a BICM block according to another embodiment of thepresent invention.

FIG. 7 illustrates a frame building block according to one embodiment ofthe present invention.

FIG. 8 illustrates an OFDM generation block according to an embodimentof the present invention.

FIG. 9 illustrates a structure of an apparatus for receiving broadcastsignals for future broadcast services according to an embodiment of thepresent invention.

FIG. 10 illustrates a frame structure according to an embodiment of thepresent invention.

FIG. 11 illustrates a signaling hierarchy structure of the frameaccording to an embodiment of the present invention.

FIG. 12 illustrates preamble signaling data according to an embodimentof the present invention.

FIG. 13 illustrates PLS1 data according to an embodiment of the presentinvention.

FIG. 14 illustrates PLS2 data according to an embodiment of the presentinvention.

FIG. 15 illustrates PLS2 data according to another embodiment of thepresent invention.

FIG. 16 illustrates a logical structure of a frame according to anembodiment of the present invention.

FIG. 17 illustrates PLS mapping according to an embodiment of thepresent invention.

FIG. 18 illustrates EAC mapping according to an embodiment of thepresent invention.

FIG. 19 illustrates FIC mapping according to an embodiment of thepresent invention.

FIG. 20 illustrates a type of DP according to an embodiment of thepresent invention.

FIG. 21 illustrates DP mapping according to an embodiment of the presentinvention.

FIG. 22 illustrates an FEC structure according to an embodiment of thepresent invention.

FIG. 23 illustrates a bit interleaving according to an embodiment of thepresent invention.

FIG. 24 illustrates a cell-word demultiplexing according to anembodiment of the present invention.

FIG. 25 illustrates a time interleaving according to an embodiment ofthe present invention.

FIG. 26 illustrates the basic operation of a twisted row-column blockinterleaver according to an embodiment of the present invention.

FIG. 27 illustrates an operation of a twisted row-column blockinterleaver according to another embodiment of the present invention.

FIG. 28 illustrates a diagonal-wise reading pattern of a twistedrow-column block interleaver according to an embodiment of the presentinvention.

FIG. 29 illustrates interleaved XFECBLOCKs from each interleaving arrayaccording to an embodiment of the present invention.

FIG. 30 shows equations that express a matrix according to the MIMOscheme according to an embodiment of the present invention.

FIG. 31 shows the MIMO parameter “a” when an NUC is applied according toan embodiment of the present invention.

FIG. 32 shows an equation that expresses a MIMO scheme in considerationof power imbalance and a correlated channel environment and an equationthat expresses a capacity of BICM according to an embodiment of thepresent invention.

FIG. 33 shows an equation that expresses a condition of a MIMO decoderfor an NUC.

FIG. 34 shows MIMO constellations and MIMO parameters “a” proposed for 8bits per cell unit (bpcu), 12 bpcu, and 16 bpcu according to anembodiment of the present invention.

FIG. 35 shows MIMO constellations and MIMO parameters “a” proposed for 8bpcu, 12 bpcu, and 16 bpcu according to another embodiment of thepresent invention.

FIG. 36 shows MIMO constellations and MIMO parameters “a” proposed for20 bpcu and 24 bpcu according to an embodiment of the present invention.

FIG. 37 shows a type of a precoding matrix of the PH-eSM schemeaccording to an embodiment of the present invention.

FIG. 38 shows a MIMO matrix of the FRFD scheme according to anembodiment of the present invention.

FIG. 39 shows signaling information for signaling a MIMO matrixaccording to an embodiment of the present invention.

FIG. 40 shows MIMO constellations and MIMO parameters proposed for 4bpcu and 8 bpcu according to another embodiment of the presentinvention.

FIG. 41 shows MIMO constellations and MIMO parameters proposed for 12bpcu, 16 bpcu and 20 bpcu according to another embodiment of the presentinvention.

FIG. 42 shows MIMO constellations and MIMO parameters proposed for 24bpcu according to another embodiment of the present invention.

FIG. 43 is a flowchart illustrating a method for receiving broadcastsignals according to an embodiment of the present invention.

DETAILED DESCRIPTION OF THE INVENTION

Reference will now be made in detail to the preferred embodiments of thepresent invention, examples of which are illustrated in the accompanyingdrawings. The detailed description, which will be given below withreference to the accompanying drawings, is intended to explain exemplaryembodiments of the present invention, rather than to show the onlyembodiments that can be implemented according to the present invention.The following detailed description includes specific details in order toprovide a thorough understanding of the present invention. However, itwill be apparent to those skilled in the art that the present inventionmay be practiced without such specific details.

Although most terms used in the present invention have been selectedfrom general ones widely used in the art, some terms have beenarbitrarily selected by the applicant and their meanings are explainedin detail in the following description as needed. Thus, the presentinvention should be understood based upon the intended meanings of theterms rather than their simple names or meanings.

The present invention provides apparatuses and methods for transmittingand receiving broadcast signals for future broadcast services. Futurebroadcast services according to an embodiment of the present inventioninclude a terrestrial broadcast service, a mobile broadcast service, aUHDTV service, etc. The present invention may process broadcast signalsfor the future broadcast services through non-MIMO (Multiple InputMultiple Output) or MIMO according to one embodiment. A non-MIMO schemeaccording to an embodiment of the present invention may include a MISO(Multiple Input Single Output) scheme, a SISO (Single Input SingleOutput) scheme, etc.

While MISO or MIMO uses two antennas in the following for convenience ofdescription, the present invention is applicable to systems using two ormore antennas.

The present invention may define three physical layer (PL)profiles—base, handheld and advanced profiles—each optimized to minimizereceiver complexity while attaining the performance required for aparticular use case. The physical layer (PHY) profiles are subsets ofall configurations that a corresponding receiver should implement.

The three PHY profiles share most of the functional blocks but differslightly in specific blocks and/or parameters. Additional PHY profilescan be defined in the future. For the system evolution, future profilescan also be multiplexed with the existing profiles in a single RFchannel through a future extension frame (FEF). The details of each PHYprofile are described below.

1. Base Profile

The base profile represents a main use case for fixed receiving devicesthat are usually connected to a roof-top antenna. The base profile alsoincludes portable devices that could be transported to a place butbelong to a relatively stationary reception category. Use of the baseprofile could be extended to handheld devices or even vehicular by someimproved implementations, but those use cases are not expected for thebase profile receiver operation.

Target SNR range of reception is from approximately 10 to 20 dB, whichincludes the 15 dB SNR reception capability of the existing broadcastsystem (e.g. ATSC A/53). The receiver complexity and power consumptionare not as critical as in the battery-operated handheld devices, whichwill use the handheld profile. Key system parameters for the baseprofile are listed in below table 1.

TABLE 1 LDPC codeword length 16K, 64K bits Constellation size 4~10 bpcu(bits per channel use) Time de-interleaving memory size ≤2¹⁹ data cellsPilot patterns Pilot pattern for fixed reception FFT size 16K, 32Kpoints

2. Handheld Profile

The handheld profile is designed for use in handheld and vehiculardevices that operate with battery power. The devices can be moving withpedestrian or vehicle speed. The power consumption as well as thereceiver complexity is very important for the implementation of thedevices of the handheld profile. The target SNR range of the handheldprofile is approximately 0 to 10 dB, but can be configured to reachbelow 0 dB when intended for deeper indoor reception.

In addition to low SNR capability, resilience to the Doppler Effectcaused by receiver mobility is the most important performance attributeof the handheld profile. Key system parameters for the handheld profileare listed in the below table 2.

TABLE 2 LDPC codeword length 16K bits Constellation size 2~8 bpcu Timede-interleaving memory size ≤2¹⁸ data cells Pilot patterns Pilotpatterns for mobile and indoor reception FFT size 8K, 16K points

3. Advanced Profile

The advanced profile provides highest channel capacity at the cost ofmore implementation complexity. This profile requires using MIMOtransmission and reception, and UHDTV service is a target use case forwhich this profile is specifically designed. The increased capacity canalso be used to allow an increased number of services in a givenbandwidth, e.g., multiple SDTV or HDTV services.

The target SNR range of the advanced profile is approximately 20 to 30dB. MIMO transmission may initially use existing elliptically-polarizedtransmission equipment, with extension to full-power cross-polarizedtransmission in the future. Key system parameters for the advancedprofile are listed in below table 3.

TABLE 3 LDPC codeword length 16K, 64K bits Constellation size 8~12 bpcuTime de-interleaving memory size ≤2¹⁹ data cells Pilot patterns Pilotpattern for fixed reception FFT size 16K, 32K points

In this case, the base profile can be used as a profile for both theterrestrial broadcast service and the mobile broadcast service. That is,the base profile can be used to define a concept of a profile whichincludes the mobile profile. Also, the advanced profile can be dividedadvanced profile for a base profile with MIMO and advanced profile for ahandheld profile with MIMO. Moreover, the three profiles can be changedaccording to intention of the designer.

The following terms and definitions may apply to the present invention.The following terms and definitions can be changed according to design.

auxiliary stream: sequence of cells carrying data of as yet undefinedmodulation and coding, which may be used for future extensions or asrequired by broadcasters or network operators

base data pipe: data pipe that carries service signaling data

baseband frame (or BBFRAME): set of Kbch bits which form the input toone FEC encoding process (BCH and LDPC encoding)

cell: modulation value that is carried by one carrier of the OFDMtransmission

coded block: LDPC-encoded block of PLS1 data or one of the LDPC-encodedblocks of PLS2 data

data pipe: logical channel in the physical layer that carries servicedata or related metadata, which may carry one or multiple service(s) orservice component(s).

data pipe unit: a basic unit for allocating data cells to a DP in aframe.

data symbol: OFDM symbol in a frame which is not a preamble symbol (theframe signaling symbol and frame edge symbol is included in the datasymbol)

DP_ID: this 8-bit field identifies uniquely a DP within the systemidentified by the SYSTEM_ID

dummy cell: cell carrying a pseudo-random value used to fill theremaining capacity not used for PLS signaling, DPs or auxiliary streams

emergency alert channel: part of a frame that carries EAS informationdata

frame: physical layer time slot that starts with a preamble and endswith a frame edge symbol

frame repetition unit: a set of frames belonging to same or differentphysical layer profile including a FEF, which is repeated eight times ina super-frame

fast information channel: a logical channel in a frame that carries themapping information between a service and the corresponding base DP

FECBLOCK: set of LDPC-encoded bits of a DP data

FFT size: nominal FFT size used for a particular mode, equal to theactive symbol period Ts expressed in cycles of the elementary period T

frame signaling symbol: OFDM symbol with higher pilot density used atthe start of a frame in certain combinations of FFT size, guard intervaland scattered pilot pattern, which carries a part of the PLS data

frame edge symbol: OFDM symbol with higher pilot density used at the endof a frame in certain combinations of FFT size, guard interval andscattered pilot pattern

frame-group: the set of all the frames having the same PHY profile typein a super-frame.

future extension frame: physical layer time slot within the super-framethat could be used for future extension, which starts with a preamble

Futurecast UTB system: proposed physical layer broadcasting system, ofwhich the input is one or more MPEG2-TS or IP or general stream(s) andof which the output is an RF signal

input stream: A stream of data for an ensemble of services delivered tothe end users by the system.

normal data symbol: data symbol excluding the frame signaling symbol andthe frame edge symbol

PHY profile: subset of all configurations that a corresponding receivershould implement

PLS: physical layer signaling data consisting of PLS1 and PLS2

PLS1: a first set of PLS data carried in the FSS symbols having a fixedsize, coding and modulation, which carries basic information about thesystem as well as the parameters needed to decode the PLS2

NOTE: PLS1 data remains constant for the duration of a frame-group.

PLS2: a second set of PLS data transmitted in the FSS symbol, whichcarries more detailed PLS data about the system and the DPs

PLS2 dynamic data: PLS2 data that may dynamically change frame-by-frame

PLS2 static data: PLS2 data that remains static for the duration of aframe-group

preamble signaling data: signaling data carried by the preamble symboland used to identify the basic mode of the system

preamble symbol: fixed-length pilot symbol that carries basic PLS dataand is located in the beginning of a frame

NOTE: The preamble symbol is mainly used for fast initial band scan todetect the system signal, its timing, frequency offset, and FFT-size.

reserved for future use: not defined by the present document but may bedefined in future

super-frame: set of eight frame repetition units

time interleaving block (TI block): set of cells within which timeinterleaving is carried out, corresponding to one use of the timeinterleaver memory

TI group: unit over which dynamic capacity allocation for a particularDP is carried out, made up of an integer, dynamically varying number ofXFECBLOCKs

NOTE: The TI group may be mapped directly to one frame or may be mappedto multiple frames. It may contain one or more TI blocks.

Type 1 DP: DP of a frame where all DPs are mapped into the frame in TDMfashion

Type 2 DP: DP of a frame where all DPs are mapped into the frame in FDMfashion

XFECBLOCK: set of Ncells cells carrying all the bits of one LDPCFECBLOCK

FIG. 1 illustrates a structure of an apparatus for transmittingbroadcast signals for future broadcast services according to anembodiment of the present invention.

The apparatus for transmitting broadcast signals for future broadcastservices according to an embodiment of the present invention can includean input formatting block 1000, a BICM (Bit interleaved coding &modulation) block 1010, a frame building block 1020, an OFDM (OrthogonalFrequency Division Multiplexing) generation block 1030 and a signalinggeneration block 1040. A description will be given of the operation ofeach module of the apparatus for transmitting broadcast signals.

IP stream/packets and MPEG2-TS are the main input formats, other streamtypes are handled as General Streams. In addition to these data inputs,Management Information is input to control the scheduling and allocationof the corresponding bandwidth for each input stream. One or multiple TSstream(s), IP stream(s) and/or General Stream(s) inputs aresimultaneously allowed.

The input formatting block 1000 can demultiplex each input stream intoone or multiple data pipe(s), to each of which an independent coding andmodulation is applied. The data pipe (DP) is the basic unit forrobustness control, thereby affecting quality-of-service (QoS). One ormultiple service(s) or service component(s) can be carried by a singleDP. Details of operations of the input formatting block 1000 will bedescribed later.

The data pipe is a logical channel in the physical layer that carriesservice data or related metadata, which may carry one or multipleservice(s) or service component(s).

Also, the data pipe unit: a basic unit for allocating data cells to a DPin a frame.

In the BICM block 1010, parity data is added for error correction andthe encoded bit streams are mapped to complex-value constellationsymbols. The symbols are interleaved across a specific interleavingdepth that is used for the corresponding DP. For the advanced profile,MIMO encoding is performed in the BICM block 1010 and the additionaldata path is added at the output for MIMO transmission. Details ofoperations of the BICM block 1010 will be described later.

The Frame Building block 1020 can map the data cells of the input DPsinto the OFDM symbols within a frame. After mapping, the frequencyinterleaving is used for frequency-domain diversity, especially tocombat frequency-selective fading channels. Details of operations of theFrame Building block 1020 will be described later.

After inserting a preamble at the beginning of each frame, the OFDMGeneration block 1030 can apply conventional OFDM modulation having acyclic prefix as guard interval. For antenna space diversity, adistributed MISO scheme is applied across the transmitters. In addition,a Peak-to-Average Power Reduction (PAPR) scheme is performed in the timedomain For flexible network planning, this proposal provides a set ofvarious FFT sizes, guard interval lengths and corresponding pilotpatterns. Details of operations of the OFDM Generation block 1030 willbe described later.

The Signaling Generation block 1040 can create physical layer signalinginformation used for the operation of each functional block. Thissignaling information is also transmitted so that the services ofinterest are properly recovered at the receiver side. Details ofoperations of the Signaling Generation block 1040 will be describedlater.

FIGS. 2, 3 and 4 illustrate the input formatting block 1000 according toembodiments of the present invention. A description will be given ofeach figure.

FIG. 2, including (a) and (b), illustrates an input formatting blockaccording to one embodiment of the present invention. FIG. 2 shows aninput formatting module when the input signal is a single input stream.

The input formatting block illustrated in FIG. 2 corresponds to anembodiment of the input formatting block 1000 described with referenceto FIG. 1.

The input to the physical layer may be composed of one or multiple datastreams. Each data stream is carried by one DP. The mode adaptationmodules slice the incoming data stream into data fields of the basebandframe (BBF). The system supports three types of input data streams:MPEG2-TS, Internet protocol (IP) and Generic stream (GS). MPEG2-TS ischaracterized by fixed length (188 byte) packets with the first bytebeing a sync-byte (0x47). An IP stream is composed of variable length IPdatagram packets, as signaled within IP packet headers. The systemsupports both IPv4 and IPv6 for the IP stream. GS may be composed ofvariable length packets or constant length packets, signaled withinencapsulation packet headers.

FIG. 2(a) shows a mode adaptation block 2000 and a stream adaptation2010 for signal DP, and FIG. 2(b) shows a PLS generation block 2020 anda PLS scrambler 2030 for generating and processing PLS data. Adescription will be given of the operation of each block.

The Input Stream Splitter splits the input TS, IP, GS streams intomultiple service or service component (audio, video, etc.) streams. Themode adaptation module 2010 is comprised of a CRC Encoder, BB (baseband)Frame Slicer, and BB Frame Header Insertion block.

The CRC Encoder provides three kinds of CRC encoding for error detectionat the user packet (UP) level, i.e., CRC-8, CRC-16, and CRC-32. Thecomputed CRC bytes are appended after the UP. CRC-8 is used for TSstream and CRC-32 for IP stream. If the GS stream doesn't provide theCRC encoding, the proposed CRC encoding should be applied.

BB Frame Slicer maps the input into an internal logical-bit format. Thefirst received bit is defined to be the MSB. The BB Frame Slicerallocates a number of input bits equal to the available data fieldcapacity. To allocate a number of input bits equal to the BBF payload,the UP packet stream is sliced to fit the data field of BBF.

BB Frame Header Insertion block can insert fixed length BBF header of 2bytes is inserted in front of the BB Frame. The BBF header is composedof STUFFI (1 bit), SYNCD (13 bits), and RFU (2 bits). In addition to thefixed 2-Byte BBF header, BBF can have an extension field (1 or 3 bytes)at the end of the 2-byte BBF header.

The stream adaptation 2010 is comprised of stuffing insertion block andBB scrambler.

The stuffing insertion block can insert stuffing field into a payload ofa BB frame. If the input data to the stream adaptation is sufficient tofill a BB-Frame, STUFFI is set to ‘0’ and the BBF has no stuffing field.Otherwise STUFFI is set to ‘1’ and the stuffing field is insertedimmediately after the BBF header. The stuffing field comprises two bytesof the stuffing field header and a variable size of stuffing data.

The BB scrambler scrambles complete BBF for energy dispersal. Thescrambling sequence is synchronous with the BBF. The scrambling sequenceis generated by the feed-back shift register.

The PLS generation block 2020 can generate physical layer signaling(PLS) data. The PLS provides the receiver with a means to accessphysical layer DPs. The PLS data consists of PLS1 data and PLS2 data.

The PLS1 data is a first set of PLS data carried in the FSS symbols inthe frame having a fixed size, coding and modulation, which carriesbasic information about the system as well as the parameters needed todecode the PLS2 data. The PLS1 data provides basic transmissionparameters including parameters required to enable the reception anddecoding of the PLS2 data. Also, the PLS1 data remains constant for theduration of a frame-group.

The PLS2 data is a second set of PLS data transmitted in the FSS symbol,which carries more detailed PLS data about the system and the DPs. ThePLS2 contains parameters that provide sufficient information for thereceiver to decode the desired DP. The PLS2 signaling further consistsof two types of parameters, PLS2 Static data (PLS2-STAT data) and PLS2dynamic data (PLS2-DYN data). The PLS2 Static data is PLS2 data thatremains static for the duration of a frame-group and the PLS2 dynamicdata is PLS2 data that may dynamically change frame-by-frame.

Details of the PLS data will be described later.

The PLS scrambler 2030 can scramble the generated PLS data for energydispersal.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 3 illustrates an input formatting block according to anotherembodiment of the present invention.

The input formatting block illustrated in FIG. 3 corresponds to anembodiment of the input formatting block 1000 described with referenceto FIG. 1.

FIG. 3 shows a mode adaptation block of the input formatting block whenthe input signal corresponds to multiple input streams.

The mode adaptation block of the input formatting block for processingthe multiple input streams can independently process the multiple inputstreams.

Referring to FIG. 3, the mode adaptation block for respectivelyprocessing the multiple input streams can include an input streamsplitter 3000, an input stream synchronizer 3010, a compensating delayblock 3020, a null packet deletion block 3030, a head compression block3040, a CRC encoder 3050, a BB frame slicer 3060 and a BB headerinsertion block 3070. Description will be given of each block of themode adaptation block.

Operations of the CRC encoder 3050, BB frame slicer 3060 and BB headerinsertion block 3070 correspond to those of the CRC encoder, BB frameslicer and BB header insertion block described with reference to FIG. 2and thus description thereof is omitted.

The input stream splitter 3000 can split the input TS, IP, GS streamsinto multiple service or service component (audio, video, etc.) streams.

The input stream synchronizer 3010 may be referred as ISSY. The ISSY canprovide suitable means to guarantee Constant Bit Rate (CBR) and constantend-to-end transmission delay for any input data format. The ISSY isalways used for the case of multiple DPs carrying TS, and optionallyused for multiple DPs carrying GS streams.

The compensating delay block 3020 can delay the split TS packet streamfollowing the insertion of ISSY information to allow a TS packetrecombining mechanism without requiring additional memory in thereceiver.

The null packet deletion block 3030, is used only for the TS inputstream case. Some TS input streams or split TS streams may have a largenumber of null-packets present in order to accommodate VBR (variablebit-rate) services in a CBR TS stream. In this case, in order to avoidunnecessary transmission overhead, null-packets can be identified andnot transmitted. In the receiver, removed null-packets can bere-inserted in the exact place where they were originally by referenceto a deleted null-packet (DNP) counter that is inserted in thetransmission, thus guaranteeing constant bit-rate and avoiding the needfor time-stamp (PCR) updating.

The head compression block 3040 can provide packet header compression toincrease transmission efficiency for TS or IP input streams. Because thereceiver can have a priori information on certain parts of the header,this known information can be deleted in the transmitter.

For Transport Stream, the receiver has a-priori information about thesync-byte configuration (0x47) and the packet length (188 Byte). If theinput TS stream carries content that has only one PID, i.e., for onlyone service component (video, audio, etc.) or service sub-component (SVCbase layer, SVC enhancement layer, MVC base view or MVC dependentviews), TS packet header compression can be applied (optionally) to theTransport Stream. IP packet header compression is used optionally if theinput steam is an IP stream.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 4 illustrates an input formatting block according to anotherembodiment of the present invention.

The input formatting block illustrated in FIG. 4 corresponds to anembodiment of the input formatting block 1000 described with referenceto FIG. 1.

FIG. 4 illustrates a stream adaptation block of the input formattingmodule when the input signal corresponds to multiple input streams.

Referring to FIG. 4, the mode adaptation block for respectivelyprocessing the multiple input streams can include a scheduler 4000, an1-Frame delay block 4010, a stuffing insertion block 4020, an in-bandsignaling 4030, a BB Frame scrambler 4040, a PLS generation block 4050and a PLS scrambler 4060. Description will be given of each block of thestream adaptation block.

Operations of the stuffing insertion block 4020, the BB Frame scrambler4040, the PLS generation block 4050 and the PLS scrambler 4060correspond to those of the stuffing insertion block, BB scrambler, PLSgeneration block and the PLS scrambler described with reference to FIG.2 and thus description thereof is omitted.

The scheduler 4000 can determine the overall cell allocation across theentire frame from the amount of FECBLOCKs of each DP. Including theallocation for PLS, EAC and FIC, the scheduler generate the values ofPLS2-DYN data, which is transmitted as in-band signaling or PLS cell inFSS of the frame. Details of FECBLOCK, EAC and FIC will be describedlater.

The 1-Frame delay block 4010 can delay the input data by onetransmission frame such that scheduling information about the next framecan be transmitted through the current frame for in-band signalinginformation to be inserted into the DPs.

The in-band signaling 4030 can insert un-delayed part of the PLS2 datainto a DP of a frame.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 5, including (a) and (b), illustrates a BICM block according to anembodiment of the present invention.

The BICM block illustrated in FIG. 5 corresponds to an embodiment of theBICM block 1010 described with reference to FIG. 1.

As described above, the apparatus for transmitting broadcast signals forfuture broadcast services according to an embodiment of the presentinvention can provide a terrestrial broadcast service, mobile broadcastservice, UHDTV service, etc.

Since QoS (quality of service) depends on characteristics of a serviceprovided by the apparatus for transmitting broadcast signals for futurebroadcast services according to an embodiment of the present invention,data corresponding to respective services needs to be processed throughdifferent schemes. Accordingly, the a BICM block according to anembodiment of the present invention can independently process DPs inputthereto by independently applying SISO, MISO and MIMO schemes to thedata pipes respectively corresponding to data paths. Consequently, theapparatus for transmitting broadcast signals for future broadcastservices according to an embodiment of the present invention can controlQoS for each service or service component transmitted through each DP.

FIG. 5(a) shows the BICM block shared by the base profile and thehandheld profile, and FIG. 5(b) shows the BICM block of the advancedprofile.

The BICM block shared by the base profile and the handheld profile andthe BICM block of the advanced profile can include plural processingblocks for processing each DP.

A description will be given of each processing block of the BICM blockfor the base profile and the handheld profile and the BICM block for theadvanced profile.

A processing block 5000 of the BICM block for the base profile and thehandheld profile can include a Data FEC encoder 5010, a bit interleaver5020, a constellation mapper 5030, an SSD (Signal Space Diversity)encoding block 5040 and a time interleaver 5050.

The Data FEC encoder 5010 can perform the FEC encoding on the input BBFto generate FECBLOCK procedure using outer coding (BCH), and innercoding (LDPC). The outer coding (BCH) is optional coding method. Detailsof operations of the Data FEC encoder 5010 will be described later.

The bit interleaver 5020 can interleave outputs of the Data FEC encoder5010 to achieve optimized performance with combination of the LDPC codesand modulation scheme while providing an efficiently implementablestructure. Details of operations of the bit interleaver 5020 will bedescribed later.

The constellation mapper 5030 can modulate each cell word from the bitinterleaver 5020 in the base and the handheld profiles, or cell wordfrom the Cell-word demultiplexer 5010-1 in the advanced profile usingeither QPSK, QAM-16, non-uniform QAM (NUQ-64, NUQ-256, NUQ-1024) ornon-uniform constellation (NUC-16, NUC-64, NUC-256, NUC-1024) to give apower-normalized constellation point, el. This constellation mapping isapplied only for DPs. Observe that QAM-16 and NUQs are square shaped,while NUCs have arbitrary shape. When each constellation is rotated byany multiple of 90 degrees, the rotated constellation exactly overlapswith its original one. This “rotation-sense” symmetric property makesthe capacities and the average powers of the real and imaginarycomponents equal to each other. Both NUQs and NUCs are definedspecifically for each code rate and the particular one used is signaledby the parameter DP_MOD filed in PLS2 data.

The SSD encoding block 5040 can precode cells in two (2D), three (3D),and four (4D) dimensions to increase the reception robustness underdifficult fading conditions.

The time interleaver 5050 can operates at the DP level. The parametersof time interleaving (TI) may be set differently for each DP. Details ofoperations of the time interleaver 5050 will be described later.

A processing block 5000-1 of the BICM block for the advanced profile caninclude the Data FEC encoder, bit interleaver, constellation mapper, andtime interleaver. However, the processing block 5000-1 is distinguishedfrom the processing block 5000 further includes a cell-worddemultiplexer 5010-1 and a MIMO encoding block 5020-1.

Also, the operations of the Data FEC encoder, bit interleaver,constellation mapper, and time interleaver in the processing block5000-1 correspond to those of the Data FEC encoder 5010, bit interleaver5020, constellation mapper 5030, and time interleaver 5050 described andthus description thereof is omitted.

The cell-word demultiplexer 5010-1 is used for the DP of the advancedprofile to divide the single cell-word stream into dual cell-wordstreams for MIMO processing. Details of operations of the cell-worddemultiplexer 5010-1 will be described later.

The MIMO encoding block 5020-1 can process the output of the cell-worddemultiplexer 5010-1 using MIMO encoding scheme. The MIMO encodingscheme was optimized for broadcasting signal transmission. The MIMOtechnology is a promising way to get a capacity increase but it dependson channel characteristics. Especially for broadcasting, the strong LOScomponent of the channel or a difference in the received signal powerbetween two antennas caused by different signal propagationcharacteristics makes it difficult to get capacity gain from MIMO. Theproposed MIMO encoding scheme overcomes this problem using arotation-based pre-coding and phase randomization of one of the MIMOoutput signals.

MIMO encoding is intended for a 2×2 MIMO system requiring at least twoantennas at both the transmitter and the receiver. Two MIMO encodingmodes are defined in this proposal; full-rate spatial multiplexing(FR-SM) and full-rate full-diversity spatial multiplexing (FRFD-SM). TheFR-SM encoding provides capacity increase with relatively smallcomplexity increase at the receiver side while the FRFD-SM encodingprovides capacity increase and additional diversity gain with a greatcomplexity increase at the receiver side. The proposed MIMO encodingscheme has no restriction on the antenna polarity configuration.

MIMO processing is required for the advanced profile frame, which meansall DPs in the advanced profile frame are processed by the MIMO encoder.MIMO processing is applied at DP level. Pairs of the ConstellationMapper outputs NUQ (e1,i and e2,i) are fed to the input of the MIMOEncoder. Paired MIMO Encoder output (g1,i and g2,i) is transmitted bythe same carrier k and OFDM symbol 1 of their respective TX antennas.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 6 illustrates a BICM block according to another embodiment of thepresent invention.

The BICM block illustrated in FIG. 6 corresponds to an embodiment of theBICM block 1010 described with reference to FIG. 1.

FIG. 6 illustrates a BICM block for protection of physical layersignaling (PLS), emergency alert channel (EAC) and fast informationchannel (FIC). EAC is a part of a frame that carries EAS informationdata and FIC is a logical channel in a frame that carries the mappinginformation between a service and the corresponding base DP. Details ofthe EAC and FIC will be described later.

Referring to FIG. 6, the BICM block for protection of PLS, EAC and FICcan include a PLS FEC encoder 6000, a bit interleaver 6010 and aconstellation mapper 6020.

Also, the PLS FEC encoder 6000 can include a scrambler, BCHencoding/zero insertion block, LDPC encoding block and LDPC paritypuncturing block. Description will be given of each block of the BICMblock.

The PLS FEC encoder 6000 can encode the scrambled PLS 1/2 data, EAC andFIC section.

The scrambler can scramble PLS 1 data and PLS2 data before BCH encodingand shortened and punctured LDPC encoding.

The BCH encoding/zero insertion block can perform outer encoding on thescrambled PLS 1/2 data using the shortened BCH code for PLS protectionand insert zero bits after the BCH encoding. For PLS1 data only, theoutput bits of the zero insertion may be permuted before LDPC encoding.

The LDPC encoding block can encode the output of the BCH encoding/zeroinsertion block using LDPC code. To generate a complete coded block,Cldpc, parity bits, Pldpc are encoded systematically from eachzero-inserted PLS information block, Ildpc and appended after it.C _(ldpc)=[I _(ldpc) P _(ldpc)]=[i ₀ ,i ₁ , . . . ,i _(K) _(ldpc) ⁻¹ ,p₀ ,p ₁ , . . . ,p _(N) _(ldpc) _(−K) _(ldpc) ⁻¹]  [Math figure 1]

The LDPC code parameters for PLS1 and PLS2 are as following table 4.

TABLE 4 Sig- naling K_(ldpc) code Type K_(sig) K_(bch) N_(bch)_parity (=N_(bch)) N_(ldpc) N_(ldpc)_parity rate Q_(ldpc) PLS1 342 1020 60 10804320 3240 1/4 36 PLS2 <1021 >1020 2100 2160 7200 5040 3/10 56

The LDPC parity puncturing block can perform puncturing on the PLS1 dataand PLS 2 data.

When shortening is applied to the PLS1 data protection, some LDPC paritybits are punctured after LDPC encoding. Also, for the PLS2 dataprotection, the LDPC parity bits of PLS2 are punctured after LDPCencoding. These punctured bits are not transmitted.

The bit interleaver 6010 can interleave the each shortened and puncturedPLS1 data and PLS2 data.

The constellation mapper 6020 can map the bit interleaved PLS1 data andPLS2 data onto constellations.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 7 illustrates a frame building block according to one embodiment ofthe present invention.

The frame building block illustrated in FIG. 7 corresponds to anembodiment of the frame building block 1020 described with reference toFIG. 1.

Referring to FIG. 7, the frame building block can include a delaycompensation block 7000, a cell mapper 7010 and a frequency interleaver7020. Description will be given of each block of the frame buildingblock.

The delay compensation block 7000 can adjust the timing between the datapipes and the corresponding PLS data to ensure that they are co-timed atthe transmitter end. The PLS data is delayed by the same amount as datapipes are by addressing the delays of data pipes caused by the InputFormatting block and BICM block. The delay of the BICM block is mainlydue to the time interleaver 5050. In-band signaling data carriesinformation of the next TI group so that they are carried one frameahead of the DPs to be signaled. The Delay Compensating block delaysin-band signaling data accordingly.

The cell mapper 7010 can map PLS, EAC, FIC, DPs, auxiliary streams anddummy cells into the active carriers of the OFDM symbols in the frame.The basic function of the cell mapper 7010 is to map data cells producedby the TIs for each of the DPs, PLS cells, and EAC/FIC cells, if any,into arrays of active OFDM cells corresponding to each of the OFDMsymbols within a frame. Service signaling data (such as PSI (programspecific information)/SI) can be separately gathered and sent by a datapipe. The Cell Mapper operates according to the dynamic informationproduced by the scheduler and the configuration of the frame structure.Details of the frame will be described later.

The frequency interleaver 7020 can randomly interleave data cellsreceived from the cell mapper 7010 to provide frequency diversity. Also,the frequency interleaver 7020 can operate on very OFDM symbol paircomprised of two sequential OFDM symbols using a differentinterleaving-seed order to get maximum interleaving gain in a singleframe.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 8 illustrates an OFDM generation block according to an embodimentof the present invention.

The OFDM generation block illustrated in FIG. 8 corresponds to anembodiment of the OFDM generation block 1030 described with reference toFIG. 1.

The OFDM generation block modulates the OFDM carriers by the cellsproduced by the Frame Building block, inserts the pilots, and producesthe time domain signal for transmission. Also, this block subsequentlyinserts guard intervals, and applies PAPR (Peak-to-Average Power Radio)reduction processing to produce the final RF signal.

Referring to FIG. 8, the OFDM generation block can include a pilot andreserved tone insertion block 8000, a 2D-eSFN encoding block 8010, anIFFT (Inverse Fast Fourier Transform) block 8020, a PAPR reduction block8030, a guard interval insertion block 8040, a preamble insertion block8050, other system insertion block 8060 and a DAC block 8070.Description will be given of each block of the frame building block.

The pilot and reserved tone insertion block 8000 can insert pilots andthe reserved tone.

Various cells within the OFDM symbol are modulated with referenceinformation, known as pilots, which have transmitted values known apriori in the receiver. The information of pilot cells is made up ofscattered pilots, continual pilots, edge pilots, FSS (frame signalingsymbol) pilots and FES (frame edge symbol) pilots. Each pilot istransmitted at a particular boosted power level according to pilot typeand pilot pattern. The value of the pilot information is derived from areference sequence, which is a series of values, one for eachtransmitted carrier on any given symbol. The pilots can be used forframe synchronization, frequency synchronization, time synchronization,channel estimation, and transmission mode identification, and also canbe used to follow the phase noise.

Reference information, taken from the reference sequence, is transmittedin scattered pilot cells in every symbol except the preamble, FSS andFES of the frame. Continual pilots are inserted in every symbol of theframe. The number and location of continual pilots depends on both theFFT size and the scattered pilot pattern. The edge carriers are edgepilots in every symbol except for the preamble symbol. They are insertedin order to allow frequency interpolation up to the edge of thespectrum. FSS pilots are inserted in FSS(s) and FES pilots are insertedin FES. They are inserted in order to allow time interpolation up to theedge of the frame.

The system according to an embodiment of the present invention supportsthe SFN network, where distributed MISO scheme is optionally used tosupport very robust transmission mode. The 2D-eSFN is a distributed MISOscheme that uses multiple TX antennas, each of which is located in thedifferent transmitter site in the SFN network.

The 2D-eSFN encoding block 8010 can process a 2D-eSFN processing todistorts the phase of the signals transmitted from multipletransmitters, in order to create both time and frequency diversity inthe SFN configuration. Hence, burst errors due to low flat fading ordeep-fading for a long time can be mitigated.

The IFFT block 8020 can modulate the output from the 2D-eSFN encodingblock 8010 using OFDM modulation scheme. Any cell in the data symbolswhich has not been designated as a pilot (or as a reserved tone) carriesone of the data cells from the frequency interleaver. The cells aremapped to OFDM carriers.

The PAPR reduction block 8030 can perform a PAPR reduction on inputsignal using various PAPR reduction algorithms in the time domain.

The guard interval insertion block 8040 can insert guard intervals andthe preamble insertion block 8050 can insert preamble in front of thesignal. Details of a structure of the preamble will be described later.The other system insertion block 8060 can multiplex signals of aplurality of broadcast transmission/reception systems in the time domainsuch that data of two or more different broadcast transmission/receptionsystems providing broadcast services can be simultaneously transmittedin the same RF signal bandwidth. In this case, the two or more differentbroadcast transmission/reception systems refer to systems providingdifferent broadcast services. The different broadcast services may referto a terrestrial broadcast service, mobile broadcast service, etc. Datarelated to respective broadcast services can be transmitted throughdifferent frames.

The DAC block 8070 can convert an input digital signal into an analogsignal and output the analog signal. The signal output from the DACblock 7800 can be transmitted through multiple output antennas accordingto the physical layer profiles. A Tx antenna according to an embodimentof the present invention can have vertical or horizontal polarity.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

FIG. 9 illustrates a structure of an apparatus for receiving broadcastsignals for future broadcast services according to an embodiment of thepresent invention.

The apparatus for receiving broadcast signals for future broadcastservices according to an embodiment of the present invention cancorrespond to the apparatus for transmitting broadcast signals forfuture broadcast services, described with reference to FIG. 1.

The apparatus for receiving broadcast signals for future broadcastservices according to an embodiment of the present invention can includea synchronization & demodulation module 9000, a frame parsing module9010, a demapping & decoding module 9020, an output processor 9030 and asignaling decoding module 9040. A description will be given of operationof each module of the apparatus for receiving broadcast signals.

The synchronization & demodulation module 9000 can receive input signalsthrough m Rx antennas, perform signal detection and synchronization withrespect to a system corresponding to the apparatus for receivingbroadcast signals and carry out demodulation corresponding to a reverseprocedure of the procedure performed by the apparatus for transmittingbroadcast signals.

The frame parsing module 9010 can parse input signal frames and extractdata through which a service selected by a user is transmitted. If theapparatus for transmitting broadcast signals performs interleaving, theframe parsing module 9010 can carry out deinterleaving corresponding toa reverse procedure of interleaving. In this case, the positions of asignal and data that need to be extracted can be obtained by decodingdata output from the signaling decoding module 9040 to restorescheduling information generated by the apparatus for transmittingbroadcast signals.

The demapping & decoding module 9020 can convert the input signals intobit domain data and then deinterleave the same as necessary. Thedemapping & decoding module 9020 can perform demapping for mappingapplied for transmission efficiency and correct an error generated on atransmission channel through decoding. In this case, the demapping &decoding module 9020 can obtain transmission parameters necessary fordemapping and decoding by decoding the data output from the signalingdecoding module 9040.

The output processor 9030 can perform reverse procedures of variouscompression/signal processing procedures which are applied by theapparatus for transmitting broadcast signals to improve transmissionefficiency. In this case, the output processor 9030 can acquirenecessary control information from data output from the signalingdecoding module 9040. The output of the output processor 8300corresponds to a signal input to the apparatus for transmittingbroadcast signals and may be MPEG-TSs, IP streams (v4 or v6) and genericstreams.

The signaling decoding module 9040 can obtain PLS information from thesignal demodulated by the synchronization & demodulation module 9000. Asdescribed above, the frame parsing module 9010, demapping & decodingmodule 9020 and output processor 9030 can execute functions thereofusing the data output from the signaling decoding module 9040.

FIG. 10, including (a)-(d), illustrates a frame structure according toan embodiment of the present invention.

FIG. 10 shows an example configuration of the frame types and FRUs in asuper-frame. FIG. 10(a) shows a super frame according to an embodimentof the present invention, FIG. 10(b) shows FRU (Frame Repetition Unit)according to an embodiment of the present invention, FIG. 10(c) showsframes of variable PHY profiles in the FRU, and FIG. 10(d) shows astructure of a frame.

A super-frame may be composed of eight FRUs. The FRU is a basicmultiplexing unit for TDM of the frames, and is repeated eight times ina super-frame.

Each frame in the FRU belongs to one of the PHY profiles, (base,handheld, advanced) or 1-BF. The maximum allowed number of the frames inthe FRU is four and a given PHY profile can appear any number of timesfrom zero times to four times in the FRU (e.g., base, base, handheld,advanced). PHY profile definitions can be extended using reserved valuesof the PHY_PROFILE in the preamble, if required.

The FEF part is inserted at the end of the FRU, if included. When theFEF is included in the FRU, the minimum number of FEFs is 8 in asuper-frame. It is not recommended that FBF parts be adjacent to eachother.

One frame is further divided into a number of OFDM symbols and apreamble. As shown in (d), the frame comprises a preamble, one or moreframe signaling symbols (FSS), normal data symbols and a frame edgesymbol (FES).

The preamble is a special symbol that enables fast Futurecast UTB systemsignal detection and provides a set of basic transmission parameters forefficient transmission and reception of the signal. The detaileddescription of the preamble will be will be described later.

The main purpose of the FSS(s) is to carry the PLS data. For fastsynchronization and channel estimation, and hence fast decoding of PLSdata, the FSS has more dense pilot pattern than the normal data symbol.The FES has exactly the same pilots as the FSS, which enablesfrequency-only interpolation within the FES and temporal interpolation,without extrapolation, for symbols immediately preceding the FES.

FIG. 11 illustrates a signaling hierarchy structure of the frameaccording to an embodiment of the present invention.

FIG. 11 illustrates the signaling hierarchy structure, which is splitinto three main parts: the preamble signaling data 11000, the PLS1 data11010 and the PLS2 data 11020. The purpose of the preamble, which iscarried by the preamble symbol in every frame, is to indicate thetransmission type and basic transmission parameters of that frame. ThePLS1 enables the receiver to access and decode the PLS2 data, whichcontains the parameters to access the DP of interest. The PLS2 iscarried in every frame and split into two main parts: PLS2-STAT data andPLS2-DYN data. The static and dynamic portion of PLS2 data is followedby padding, if necessary.

FIG. 12 illustrates preamble signaling data according to an embodimentof the present invention.

Preamble signaling data carries 21 bits of information that are neededto enable the receiver to access PLS data and trace DPs within the framestructure. Details of the preamble signaling data are as follows:

PHY_PROFILE: This 3-bit field indicates the PHY profile type of thecurrent frame. The mapping of different PHY profile types is given inbelow table 5.

TABLE 5 Value PHY profile 000 Base profile 001 Handheld profile 010Advanced profiled 011~110 Reserved 111 FEF

FFT_SIZE: This 2 bit field indicates the FFT size of the current framewithin a frame-group, as described in below table 6.

TABLE 6 Value FFT size 00  8K FFT 01 16K FFT 10 32K FFT 11 Reserved

GI_FRACTION: This 3 bit field indicates the guard interval fractionvalue in the current super-frame, as described in below table 7.

TABLE 7 Value GI_FRACTION 000 1/5  001 1/10 010 1/20 011 1/40 100 1/80101  1/160 110~111 Reserved

EAC_FLAG: This 1 bit field indicates whether the EAC is provided in thecurrent frame. If this field is set to ‘1’, emergency alert service(EAS) is provided in the current frame. If this field set to ‘0’, EAS isnot carried in the current frame. This field can be switched dynamicallywithin a super-frame.

PILOT_MODE: This 1-bit field indicates whether the pilot mode is mobilemode or fixed mode for the current frame in the current frame-group. Ifthis field is set to ‘0’, mobile pilot mode is used. If the field is setto ‘1’, the fixed pilot mode is used.

PAPR_FLAG: This 1-bit field indicates whether PAPR reduction is used forthe current frame in the current frame-group. If this field is set tovalue ‘1’, tone reservation is used for PAPR reduction. If this field isset to ‘0’, PAPR reduction is not used.

FRU_CONFIGURE: This 3-bit field indicates the PHY profile typeconfigurations of the frame repetition units (FRU) that are present inthe current super-frame. All profile types conveyed in the currentsuper-frame are identified in this field in all preambles in the currentsuper-frame. The 3-bit field has a different definition for eachprofile, as show in below table 8.

TABLE 8 Current Current Current PHY_ PHY_ PHY_ Current PROFILE = PROFILE= ‘001’ PROFILE = ‘010’ PHY_PROFILE = ‘000’ (base) (handheld) (advanced)‘111’ (FEF) FRU_CONFIGURE = Only base Only handheld Only advanced OnlyFEF 000 profile profile present profile present present presentFRU_CONFIGURE = Handheld Base profile Base profile Base profile 1XXprofile present present present present FRU_CONFIGURE = AdvancedAdvanced Handheld Handheld X1X profile profile profile profile presentpresent present present FRU_CONFIGURE = FEF FEF FEF Advanced XX1 presentpresent present profile present

RESERVED: This 7-bit field is reserved for future use.

FIG. 13 illustrates PLS1 data according to an embodiment of the presentinvention.

PLS1 data provides basic transmission parameters including parametersrequired to enable the reception and decoding of the PLS2. As abovementioned, the PLS1 data remain unchanged for the entire duration of oneframe-group. The detailed definition of the signaling fields of the PLS1data are as follows:

PREAMBLE_DATA: This 20-bit field is a copy of the preamble signalingdata excluding the EAC_FLAG.

NUM_FRAME_FRU: This 2-bit field indicates the number of the frames perFRU.

PAYLOAD_TYPE: This 3-bit field indicates the format of the payload datacarried in the frame-group. PAYLOAD_TYPE is signaled as shown in table9.

TABLE 9 value Payload type 1XX TS stream is transmitted X1X IP stream istransmitted XX1 GS stream is transmitted

NUM_FSS: This 2-bit field indicates the number of FSS symbols in thecurrent frame.

SYSTEM_VERSION: This 8-bit field indicates the version of thetransmitted signal format. The SYSTEM_VERSION is divided into two 4-bitfields, which are a major version and a minor version.

Major version: The MSB four bits of SYSTEM_VERSION field indicate majorversion information. A change in the major version field indicates anon-backward-compatible change. The default value is ‘0000’. For theversion described in this standard, the value is set to ‘0000’.

Minor version: The LSB four bits of SYSTEM_VERSION field indicate minorversion information. A change in the minor version field isbackward-compatible.

CELL_ID: This is a 16-bit field which uniquely identifies a geographiccell in an ATSC network. An ATSC cell coverage area may consist of oneor more frequencies, depending on the number of frequencies used perFuturecast UTB system. If the value of the CELL_ID is not known orunspecified, this field is set to ‘0’.

NETWORK_ID: This is a 16-bit field which uniquely identifies the currentATSC network.

SYSTEM_ID: This 16-bit field uniquely identifies the Futurecast UTBsystem within the ATSC network. The Futurecast UTB system is theterrestrial broadcast system whose input is one or more input streams(TS, IP, GS) and whose output is an RF signal. The Futurecast UTB systemcarries one or more PHY profiles and FEF, if any. The same FuturecastUTB system may carry different input streams and use different RFfrequencies in different geographical areas, allowing local serviceinsertion. The frame structure and scheduling are controlled in oneplace and is identical for all transmissions within a Futurecast UTBsystem. One or more Futurecast UTB systems may have the same SYSTEM_IDmeaning that they all have the same physical layer structure andconfiguration.

The following loop consists of FRU_PHY_PROFILE, FRU_FRAME_LENGTH,FRU_GI_FRACTION, and RESERVED which are used to indicate the FRUconfiguration and the length of each frame type. The loop size is fixedso that four PHY profiles (including a FEF) are signaled within the FRU.If NUM_FRAME_FRU is less than 4, the unused fields are filled withzeros.

FRU_PHY_PROFILE: This 3-bit field indicates the PHY profile type of the(i+1)th (i is the loop index) frame of the associated FRU. This fielduses the same signaling format as shown in the table 8.

FRU_FRAME_LENGTH: This 2-bit field indicates the length of the (i+1)thframe of the associated FRU. Using FRU_FRAME_LENGTH together withFRU_GI_FRACTION, the exact value of the frame duration can be obtained.

FRU_GI_FRACTION: This 3-bit field indicates the guard interval fractionvalue of the (i+1)th frame of the associated FRU. FRU_GI_FRACTION issignaled according to the table 7.

RESERVED: This 4-bit field is reserved for future use.

The following fields provide parameters for decoding the PLS2 data.

PLS2_FEC_TYPE: This 2-bit field indicates the FEC type used by the PLS2protection. The FEC type is signaled according to table 10. The detailsof the LDPC codes will be described later.

TABLE 10 Content PLS2 FEC type 00 4K-1/4 and 7K-3/10 LDPC codes 01~11Reserved

PLS2_MOD: This 3-bit field indicates the modulation type used by thePLS2. The modulation type is signaled according to table 11.

TABLE 11 Value PLS2_MODE 000 BPSK 001 QPSK 010 QAM-16 011 NUQ-64 100~111Reserved

PLS2_SIZE_CELL: This 15-bit field indicates Ctotal_partial_block, thesize (specified as the number of QAM cells) of the collection of fullcoded blocks for PLS2 that is carried in the current frame-group. Thisvalue is constant during the entire duration of the current frame-group.

PLS2_STAT_SIZE_BIT: This 14-bit field indicates the size, in bits, ofthe PLS2-STAT for the current frame-group. This value is constant duringthe entire duration of the current frame-group.

PLS2_DYN_SIZE_BIT: This 14-bit field indicates the size, in bits, of thePLS2-DYN for the current frame-group. This value is constant during theentire duration of the current frame-group.

PLS2_REP_FLAG: This 1-bit flag indicates whether the PLS2 repetitionmode is used in the current frame-group. When this field is set to value‘1’, the PLS2 repetition mode is activated. When this field is set tovalue ‘0’, the PLS2 repetition mode is deactivated.

PLS2_REP_SIZE_CELL: This 15-bit field indicates Ctotal_partial_block,the size (specified as the number of QAM cells) of the collection ofpartial coded blocks for PLS2 carried in every frame of the currentframe-group, when PLS2 repetition is used. If repetition is not used,the value of this field is equal to 0. This value is constant during theentire duration of the current frame-group.

PLS2_NEXT_FEC_TYPE: This 2-bit field indicates the FEC type used forPLS2 that is carried in every frame of the next frame-group. The FECtype is signaled according to the table 10.

PLS2_NEXT_MOD: This 3-bit field indicates the modulation type used forPLS2 that is carried in every frame of the next frame-group. Themodulation type is signaled according to the table 11.

PLS2_NEXT_REP_FLAG: This 1-bit flag indicates whether the PLS2repetition mode is used in the next frame-group. When this field is setto value ‘1’, the PLS2 repetition mode is activated. When this field isset to value ‘0’, the PLS2 repetition mode is deactivated.

PLS2_NEXT_REP_SIZE_CELL: This 15-bit field indicates Ctotal_full_block,the size (specified as the number of QAM cells) of the collection offull coded blocks for PLS2 that is carried in every frame of the nextframe-group, when PLS2 repetition is used. If repetition is not used inthe next frame-group, the value of this field is equal to 0. This valueis constant during the entire duration of the current frame-group.

PLS2_NEXT_REP_STAT_SIZE_BIT: This 14-bit field indicates the size, inbits, of the PLS2-STAT for the next frame-group. This value is constantin the current frame-group.

PLS2_NEXT_REP_DYN_SIZE_BIT: This 14-bit field indicates the size, inbits, of the PLS2-DYN for the next frame-group. This value is constantin the current frame-group.

PLS2_AP_MODE: This 2-bit field indicates whether additional parity isprovided for PLS2 in the current frame-group. This value is constantduring the entire duration of the current frame-group. The below table12 gives the values of this field. When this field is set to ‘00’,additional parity is not used for the PLS2 in the current frame-group.

TABLE 12 Value PLS2-AP mode 00 AP is not provided 01 AP1 mode 10~11Reserved

PLS2_AP_SIZE_CELL: This 15-bit field indicates the size (specified asthe number of QAM cells) of the additional parity bits of the PLS2. Thisvalue is constant during the entire duration of the current frame-group.

PLS2_NEXT_AP_MODE: This 2-bit field indicates whether additional parityis provided for PLS2 signaling in every frame of next frame-group. Thisvalue is constant during the entire duration of the current frame-group.The table 12 defines the values of this field

PLS2_NEXT_AP_SIZE_CELL: This 15-bit field indicates the size (specifiedas the number of QAM cells) of the additional parity bits of the PLS2 inevery frame of the next frame-group. This value is constant during theentire duration of the current frame-group.

RESERVED: This 32-bit field is reserved for future use.

CRC_32: A 32-bit error detection code, which is applied to the entirePLS1 signaling.

FIG. 14 illustrates PLS2 data according to an embodiment of the presentinvention.

FIG. 14 illustrates PLS2-STAT data of the PLS2 data. The PLS2-STAT dataare the same within a frame-group, while the PLS2-DYN data provideinformation that is specific for the current frame.

The details of fields of the PLS2-STAT data are as follows:

FIC_FLAG: This 1-bit field indicates whether the FIC is used in thecurrent frame-group. If this field is set to ‘1’, the FIC is provided inthe current frame. If this field set to ‘0’, the FIC is not carried inthe current frame. This value is constant during the entire duration ofthe current frame-group.

AUX_FLAG: This 1-bit field indicates whether the auxiliary stream(s) isused in the current frame-group. If this field is set to ‘1’, theauxiliary stream is provided in the current frame. If this field set to‘0’, the auxiliary stream is not carried in the current frame. Thisvalue is constant during the entire duration of current frame-group.

NUM_DP: This 6-bit field indicates the number of DPs carried within thecurrent frame. The value of this field ranges from 1 to 64, and thenumber of DPs is NUM_DP+1.

DP_ID: This 6-bit field identifies uniquely a DP within a PHY profile.

DP_TYPE: This 3-bit field indicates the type of the DP. This is signaledaccording to the below table 13.

TABLE 13 Value DP Type 000 DP Type 1 001 DP Type 2 010~111 reserved

DP_GROUP_ID: This 8-bit field identifies the DP group with which thecurrent DP is associated. This can be used by a receiver to access theDPs of the service components associated with a particular service,which will have the same DP_GROUP_ID.

BASE_DP_ID: This 6-bit field indicates the DP carrying service signalingdata (such as PSI/SI) used in the Management layer. The DP indicated byBASE_DP_ID may be either a normal DP carrying the service signaling dataalong with the service data or a dedicated DP carrying only the servicesignaling data

DP_FEC_TYPE: This 2-bit field indicates the FEC type used by theassociated DP. The FEC type is signaled according to the below table 14.

TABLE 14 Value FEC_TYPE 00 16K LDPC 01 64K LDPC 10~11 Reserved

DP_COD: This 4-bit field indicates the code rate used by the associatedDP. The code rate is signaled according to the below table 15.

TABLE 15 Value Code rate 0000  5/15 0001  6/15 0010  7/15 0011  8/150100  9/15 0101 10/15 0110 11/15 0111 12/15 1000 13/15 1001~1111Reserved

DP_MOD: This 4-bit field indicates the modulation used by the associatedDP. The modulation is signaled according to the below table 16.

TABLE 16 Value Modulation 0000 QPSK 0001 QAM-16 0010 NUQ-64 0011 NUQ-2560100 NUQ-1024 0101 NUC-16 0110 NUC-64 0111 NUC-256 1000 NUC-10241001~1111 reserved

DP_SSD_FLAG: This 1-bit field indicates whether the SSD mode is used inthe associated DP. If this field is set to value ‘1’, SSD is used. Ifthis field is set to value ‘0’, SSD is not used.

The following field appears only if PHY_PROFILE is equal to ‘010’, whichindicates the advanced profile:

DP_MIMO: This 3-bit field indicates which type of MIMO encoding processis applied to the associated DP. The type of MIMO encoding process issignaled according to the table 17.

TABLE 17 Value MIMO encoding 000 FR-SM 001 FRFD-SM 010~111 reserved

DP_TI_TYPE: This 1-bit field indicates the type of time-interleaving. Avalue of ‘0’ indicates that one TI group corresponds to one frame andcontains one or more TI-blocks. A value of ‘1’ indicates that one TIgroup is carried in more than one frame and contains only one TI-block.

DP_TI_LENGTH: The use of this 2-bit field (the allowed values are only1, 2, 4, 8) is determined by the values set within the DP_TI_TYPE fieldas follows:

If the DP_TI_TYPE is set to the value ‘1’, this field indicates PI, thenumber of the frames to which each TI group is mapped, and there is oneTI-block per TI group (NTI=1). The allowed PI values with 2-bit fieldare defined in the below table 18.

If the DP_TI_TYPE is set to the value ‘0’, this field indicates thenumber of TI-blocks NTI per TI group, and there is one TI group perframe (PI=1). The allowed PI values with 2-bit field are defined in thebelow table 18.

TABLE 18 2-bit field P_(I) N_(TI) 00 1 1 01 2 2 10 4 3 11 8 4

DP_FRAME_INTERVAL: This 2-bit field indicates the frame interval (HUMP)within the frame-group for the associated DP and the allowed values are1, 2, 4, 8 (the corresponding 2-bit field is ‘00’, ‘01’, ‘10’, or ‘11’,respectively). For DPs that do not appear every frame of theframe-group, the value of this field is equal to the interval betweensuccessive frames. For example, if a DP appears on the frames 1, 5, 9,13, etc., this field is set to ‘4’. For DPs that appear in every frame,this field is set to ‘1’.

DP_TI_BYPASS: This 1-bit field determines the availability of timeinterleaver 5050. If time interleaving is not used for a DP, it is setto ‘1’. Whereas if time interleaving is used it is set to ‘0’.

DP_FIRST_FRAME_IDX: This 5-bit field indicates the index of the firstframe of the super-frame in which the current DP occurs. The value ofDP_FIRST_FRAME_IDX ranges from 0 to 31

DP_NUM_BLOCK_MAX: This 10-bit field indicates the maximum value ofDP_NUM_BLOCKS for this DP. The value of this field has the same range asDP_NUM_BLOCKS.

DP_PAYLOAD_TYPE: This 2-bit field indicates the type of the payload datacarried by the given DP. DP_PAYLOAD_TYPE is signaled according to thebelow table 19.

TABLE 19 Value Payload Type 00 TS. 01 IP 10 GS 11 reserved

DP_INBAND_MODE: This 2-bit field indicates whether the current DPcarries in-band signaling information. The in-band signaling type issignaled according to the below table 20.

TABLE 20 Value In-band mode 00 In-band signaling is not carried. 01INBAND-PLS is carried only 10 INBAND-ISSY is carried only 11 INBAND-PLSand INBAND-ISSY are carried

DP_PROTOCOL_TYPE: This 2-bit field indicates the protocol type of thepayload carried by the given DP. It is signaled according to the belowtable 21 when input payload types are selected.

TABLE 21 If DP_ If DP_ If DP_ PAYLOAD_TYPE PAYLOAD_TYPE PAYLOAD_TYPEValue Is TS Is IP Is GS 00 MPEG2-TS IPv4 (Note) 01 Reserved IPv6Reserved 10 Reserved Reserved Reserved 11 Reserved Reserved Reserved

DP_CRC_MODE: This 2-bit field indicates whether CRC encoding is used inthe Input Formatting block. The CRC mode is signaled according to thebelow table 22.

TABLE 22 Value CRC mode 00 Not used 01 CRC-8 10 CRC-16 11 CRC-32

DNP_MODE: This 2-bit field indicates the null-packet deletion mode usedby the associated DP when DP_PAYLOAD_TYPE is set to TS (‘00’). DNP_MODEis signaled according to the below table 23. If DP_PAYLOAD_TYPE is notTS (‘00’), DNP_MODE is set to the value ‘00’.

TABLE 23 Value Null-packet deletion mode 00 Not used 01 DNP-NORMAL 10DNP-OFFSET 11 reserved

ISSY_MODE: This 2-bit field indicates the ISSY mode used by theassociated DP when DP_PAYLOAD_TYPE is set to TS (‘00’). The ISSY_MODE issignaled according to the below table 24 If DP_PAYLOAD_TYPE is not TS(‘00’), ISSY_MODE is set to the value ‘00’.

TABLE 24 Value ISSY mode 00 Not used 01 ISSY-UP 10 ISSY-BBF 11 reserved

HC_MODE_TS: This 2-bit field indicates the TS header compression modeused by the associated DP when DP_PAYLOAD_TYPE is set to TS (‘00’). TheHC_MODE_TS is signaled according to the below table 25.

TABLE 25 Value Header compression mode 00 HC_MODE_TS 1 01 HC_MODE_TS 210 HC_MODE_TS 3 11 HC_MODE_TS 4

HC_MODE_IP: This 2-bit field indicates the IP header compression modewhen DP_PAYLOAD_TYPE is set to IP (‘01’). The HC_MODE_IP is signaledaccording to the below table 26.

TABLE 26 Value Header compression mode 00 No compression 01 HC_MODE_IP 110~41 reserved

PID: This 13-bit field indicates the PID number for TS headercompression when DP_PAYLOAD_TYPE is set to TS (‘00’) and HC_MODE_TS isset to ‘01’ or ‘10’.

RESERVED: This 8-bit field is reserved for future use.

The following field appears only if FIC_FLAG is equal to ‘1’:

FIC_VERSION: This 8-bit field indicates the version number of the FIC.

FIC_LENGTH_BYTE: This 13-bit field indicates the length, in bytes, ofthe FIC.

RESERVED: This 8-bit field is reserved for future use.

The following field appears only if AUX_FLAG is equal to ‘1’:

NUM_AUX: This 4-bit field indicates the number of auxiliary streams.Zero means no auxiliary streams are used.

AUX_CONFIG_RFU: This 8-bit field is reserved for future use.

AUX_STREAM_TYPE: This 4-bit is reserved for future use for indicatingthe type of the current auxiliary stream.

AUX_PRIVATE_CONFIG: This 28-bit field is reserved for future use forsignaling auxiliary streams.

FIG. 15 illustrates PLS2 data according to another embodiment of thepresent invention.

FIG. 15 illustrates PLS2-DYN data of the PLS2 data. The values of thePLS2-DYN data may change during the duration of one frame-group, whilethe size of fields remains constant.

The details of fields of the PLS2-DYN data are as follows:

FRAME_INDEX: This 5-bit field indicates the frame index of the currentframe within the super-frame. The index of the first frame of thesuper-frame is set to ‘0’.

PLS_CHANGE_COUNTER: This 4-bit field indicates the number ofsuper-frames ahead where the configuration will change. The nextsuper-frame with changes in the configuration is indicated by the valuesignaled within this field. If this field is set to the value ‘0000’, itmeans that no scheduled change is foreseen: e.g., value ‘1’ indicatesthat there is a change in the next super-frame.

FIC_CHANGE_COUNTER: This 4-bit field indicates the number ofsuper-frames ahead where the configuration (i.e., the contents of theFIC) will change. The next super-frame with changes in the configurationis indicated by the value signaled within this field. If this field isset to the value ‘0000’, it means that no scheduled change is foreseen:e.g. value ‘0001’ indicates that there is a change in the nextsuper-frame.

RESERVED: This 16-bit field is reserved for future use.

The following fields appear in the loop over NUM_DP, which describe theparameters associated with the DP carried in the current frame.

DP_ID: This 6-bit field indicates uniquely the DP within a PHY profile.

DP_START: This 15-bit (or 13-bit) field indicates the start position ofthe first of the DPs using the DPU addressing scheme. The DP_START fieldhas differing length according to the PHY profile and FFT size as shownin the below table 27.

TABLE 27 DP_START field size PHY profile 64K 16K Base 13 bit 15 bitHandheld — 13 bit Advanced 13 bit 15 bit

DP_NUM_BLOCK: This 10-bit field indicates the number of FEC blocks inthe current TI group for the current DP. The value of DP_NUM_BLOCKranges from 0 to 1023

RESERVED: This 8-bit field is reserved for future use.

The following fields indicate the FIC parameters associated with theEAC.

EAC_FLAG: This 1-bit field indicates the existence of the EAC in thecurrent frame. This bit is the same value as the EAC_FLAG in thepreamble.

EAS_WAKE_UP_VERSION_NUM: This 8-bit field indicates the version numberof a wake-up indication.

If the EAC_FLAG field is equal to ‘1’, the following 12 bits areallocated for EAC_LENGTH_BYTE field. If the EAC_FLAG field is equal to‘0’, the following 12 bits are allocated for EAC_COUNTER.

EAC_LENGTH_BYTE: This 12-bit field indicates the length, in byte, of theEAC.

EAC_COUNTER: This 12-bit field indicates the number of the frames beforethe frame where the EAC arrives.

The following field appears only if the AUX_FLAG field is equal to ‘1’:

AUX_PRIVATE_DYN: This 48-bit field is reserved for future use forsignaling auxiliary streams. The meaning of this field depends on thevalue of AUX_STREAM_TYPE in the configurable PLS2-STAT.

CRC_32: A 32-bit error detection code, which is applied to the entirePLS2.

FIG. 16 illustrates a logical structure of a frame according to anembodiment of the present invention.

As above mentioned, the PLS, EAC, FIC, DPs, auxiliary streams and dummycells are mapped into the active carriers of the OFDM symbols in theframe. The PLS1 and PLS2 are first mapped into one or more FSS(s). Afterthat, EAC cells, if any, are mapped immediately following the PLS field,followed next by FIC cells, if any. The DPs are mapped next after thePLS or EAC, FIC, if any. Type 1 DPs follows first, and Type 2 DPs next.The details of a type of the DP will be described later. In some case,DPs may carry some special data for EAS or service signaling data. Theauxiliary stream or streams, if any, follow the DPs, which in turn arefollowed by dummy cells. Mapping them all together in the abovementioned order, i.e. PLS, EAC, FIC, DPs, auxiliary streams and dummydata cells exactly fill the cell capacity in the frame.

FIG. 17 illustrates PLS mapping according to an embodiment of thepresent invention.

PLS cells are mapped to the active carriers of FSS(s). Depending on thenumber of cells occupied by PLS, one or more symbols are designated asFSS(s), and the number of FSS(s) NFSS is signaled by NUM_FSS in PLS1.The FSS is a special symbol for carrying PLS cells. Since robustness andlatency are critical issues in the PLS, the FSS(s) has higher density ofpilots allowing fast synchronization and frequency-only interpolationwithin the FSS.

PLS cells are mapped to active carriers of the NFSS FSS(s) in a top-downmanner as shown in an example in FIG. 17. The PLS1 cells are mappedfirst from the first cell of the first FSS in an increasing order of thecell index. The PLS2 cells follow immediately after the last cell of thePLS1 and mapping continues downward until the last cell index of thefirst FSS. If the total number of required PLS cells exceeds the numberof active carriers of one FSS, mapping proceeds to the next FSS andcontinues in exactly the same manner as the first FSS.

After PLS mapping is completed, DPs are carried next. If EAC, FIC orboth are present in the current frame, they are placed between PLS and“normal” DPs.

FIG. 18 illustrates EAC mapping according to an embodiment of thepresent invention.

EAC is a dedicated channel for carrying EAS messages and links to theDPs for EAS. EAS support is provided but EAC itself may or may not bepresent in every frame. EAC, if any, is mapped immediately after thePLS2 cells. EAC is not preceded by any of the FIC, DPs, auxiliarystreams or dummy cells other than the PLS cells. The procedure ofmapping the EAC cells is exactly the same as that of the PLS.

The EAC cells are mapped from the next cell of the PLS2 in increasingorder of the cell index as shown in the example in FIG. 18. Depending onthe EAS message size, EAC cells may occupy a few symbols, as shown inFIG. 18.

EAC cells follow immediately after the last cell of the PLS2, andmapping continues downward until the last cell index of the last FSS. Ifthe total number of required EAC cells exceeds the number of remainingactive carriers of the last FSS mapping proceeds to the next symbol andcontinues in exactly the same manner as FSS(s). The next symbol formapping in this case is the normal data symbol, which has more activecarriers than a FSS.

After EAC mapping is completed, the FIC is carried next, if any exists.If FIC is not transmitted (as signaled in the PLS2 field), DPs followimmediately after the last cell of the EAC.

FIG. 19, including (a) and (b), illustrates FIC mapping according to anembodiment of the present invention.

FIG. 19(a) shows an example mapping of FIC cell without EAC, and FIG.19(b) shows an example mapping of FIC cell with EAC.

FIC is a dedicated channel for carrying cross-layer information toenable fast service acquisition and channel scanning. This informationprimarily includes channel binding information between DPs and theservices of each broadcaster. For fast scan, a receiver can decode FICand obtain information such as broadcaster ID, number of services, andBASE_DP_ID. For fast service acquisition, in addition to FIC, base DPcan be decoded using BASE_DP_ID. Other than the content it carries, abase DP is encoded and mapped to a frame in exactly the same way as anormal DP. Therefore, no additional description is required for a baseDP. The FIC data is generated and consumed in the Management Layer. Thecontent of FIC data is as described in the Management Layerspecification.

The FIC data is optional and the use of FIC is signaled by the FIC_FLAGparameter in the static part of the PLS2. If FIC is used, FIC_FLAG isset to ‘1’ and the signaling field for FIC is defined in the static partof PLS2. Signaled in this field are FIC_VERSION, and FIC_LENGTH_BYTE.FIC uses the same modulation, coding and time interleaving parameters asPLS2. FIC shares the same signaling parameters such as PLS2_MOD andPLS2_FEC. FIC data, if any, is mapped immediately after PLS2 or EAC ifany. FIC is not preceded by any normal DPs, auxiliary streams or dummycells. The method of mapping FIC cells is exactly the same as that ofEAC which is again the same as PLS.

Without EAC after PLS, FIC cells are mapped from the next cell of thePLS2 in an increasing order of the cell index as shown in an example in(a). Depending on the FIC data size, FIC cells may be mapped over a fewsymbols, as shown in (b).

FIC cells follow immediately after the last cell of the PLS2, andmapping continues downward until the last cell index of the last FSS. Ifthe total number of required FIC cells exceeds the number of remainingactive carriers of the last FSS, mapping proceeds to the next symbol andcontinues in exactly the same manner as FSS(s). The next symbol formapping in this case is the normal data symbol which has more activecarriers than a FSS.

If EAS messages are transmitted in the current frame, EAC precedes FIC,and FIC cells are mapped from the next cell of the EAC in an increasingorder of the cell index as shown in (b).

After FIC mapping is completed, one or more DPs are mapped, followed byauxiliary streams, if any, and dummy cells.

FIG. 20, including (a) and (b), illustrates a type of DP according to anembodiment of the present invention.

FIG. 20(a) shows type 1 DP, and FIG. 20(b) shows type 2 DP.

After the preceding channels, i.e., PLS, EAC and FIC, are mapped, cellsof the DPs are mapped. A DP is categorized into one of two typesaccording to mapping method:

Type 1 DP: DP is mapped by TDM

Type 2 DP: DP is mapped by FDM

The type of DP is indicated by DP_TYPE field in the static part of PLS2.FIG. 20 illustrates the mapping orders of Type 1 DPs and Type 2 DPs.Type 1 DPs are first mapped in the increasing order of cell index, andthen after reaching the last cell index, the symbol index is increasedby one. Within the next symbol, the DP continues to be mapped in theincreasing order of cell index starting from p=0. With a number of DPsmapped together in one frame, each of the Type 1 DPs are grouped intime, similar to TDM multiplexing of DPs.

Type 2 DPs are first mapped in the increasing order of symbol index, andthen after reaching the last OFDM symbol of the frame, the cell indexincreases by one and the symbol index rolls back to the first availablesymbol and then increases from that symbol index. After mapping a numberof DPs together in one frame, each of the Type 2 DPs are grouped infrequency together, similar to FDM multiplexing of DPs.

Type 1 DPs and Type 2 DPs can coexist in a frame if needed with onerestriction; Type 1 DPs always precede Type 2 DPs. The total number ofOFDM cells carrying Type 1 and Type 2 DPs cannot exceed the total numberof OFDM cells available for transmission of DPs:D _(DP1) +D _(DP2) ≤D _(DP)  [Expression 2]

where DDP1 is the number of OFDM cells occupied by Type 1 DPs, DDP2 isthe number of cells occupied by Type 2 DPs. Since PLS, EAC, FIC are allmapped in the same way as Type 1 DP, they all follow “Type 1 mappingrule”. Hence, overall, Type 1 mapping always precedes Type 2 mapping.

FIG. 21, including (a) and (b), illustrates DP mapping according to anembodiment of the present invention.

FIG. 21(a) shows an addressing of OFDM cells for mapping type 1 DPs andFIG. 21(b) shows an addressing of OFDM cells for mapping for type 2 DPs.

Addressing of OFDM cells for mapping Type 1 DPs (0, . . . , DDP1-1) isdefined for the active data cells of Type 1 DPs. The addressing schemedefines the order in which the cells from the TIs for each of the Type 1DPs are allocated to the active data cells. It is also used to signalthe locations of the DPs in the dynamic part of the PLS2.

Without EAC and FIC, address 0 refers to the cell immediately followingthe last cell carrying PLS in the last FSS. If EAC is transmitted andFIC is not in the corresponding frame, address 0 refers to the cellimmediately following the last cell carrying EAC. If FIC is transmittedin the corresponding frame, address 0 refers to the cell immediatelyfollowing the last cell carrying FIC. Address 0 for Type 1 DPs can becalculated considering two different cases as shown in (a). In theexample in (a), PLS, EAC and FIC are assumed to be all transmitted.Extension to the cases where either or both of EAC and FIC are omittedis straightforward. If there are remaining cells in the FSS aftermapping all the cells up to FIC as shown on the left side of (a).

Addressing of OFDM cells for mapping Type 2 DPs (0, . . . , DDP2-1) isdefined for the active data cells of Type 2 DPs. The addressing schemedefines the order in which the cells from the TIs for each of the Type 2DPs are allocated to the active data cells. It is also used to signalthe locations of the DPs in the dynamic part of the PLS2.

Three slightly different cases are possible as shown in (b). For thefirst case shown on the left side of (b), cells in the last FSS areavailable for Type 2 DP mapping. For the second case shown in themiddle, FIC occupies cells of a normal symbol, but the number of FICcells on that symbol is not larger than CFSS. The third case, shown onthe right side in (b), is the same as the second case except that thenumber of FIC cells mapped on that symbol exceeds CFSS.

The extension to the case where Type 1 DP(s) precede Type 2 DP(s) isstraightforward since PLS, EAC and FIC follow the same “Type 1 mappingrule” as the Type 1 DP(s).

A data pipe unit (DPU) is a basic unit for allocating data cells to a DPin a frame.

A DPU is defined as a signaling unit for locating DPs in a frame. A CellMapper 7010 may map the cells produced by the TIs for each of the DPs. ATime interleaver 5050 outputs a series of TI-blocks and each TI-blockcomprises a variable number of XFECBLOCKs which is in turn composed of aset of cells. The number of cells in an XFECBLOCK, Ncells, is dependenton the FECBLOCK size, Nldpc, and the number of transmitted bits perconstellation symbol. A DPU is defined as the greatest common divisor ofall possible values of the number of cells in a XFECBLOCK, Ncells,supported in a given PHY profile. The length of a DPU in cells isdefined as LDPU. Since each PHY profile supports different combinationsof FECBLOCK size and a different number of bits per constellationsymbol, LDPU is defined on a PHY profile basis.

FIG. 22 illustrates an FEC structure according to an embodiment of thepresent invention.

FIG. 22 illustrates an FEC structure according to an embodiment of thepresent invention before bit interleaving. As above mentioned, Data FECencoder may perform the FEC encoding on the input BBF to generateFECBLOCK procedure using outer coding (BCH), and inner coding (LDPC).The illustrated FEC structure corresponds to the FECBLOCK. Also, theFECBLOCK and the FEC structure have same value corresponding to a lengthof LDPC codeword.

The BCH encoding is applied to each BBF (Kbch bits), and then LDPCencoding is applied to BCH-encoded BBF (Kldpc bits=Nbch bits) asillustrated in FIG. 22.

The value of Nldpc is either 64800 bits (long FECBLOCK) or 16200 bits(short FECBLOCK).

The below table 28 and table 29 show FEC encoding parameters for a longFECBLOCK and a short FECBLOCK, respectively.

TABLE 28 BCH error LDPC correction N_(bch)- Rate N_(ldpc) K_(ldpc)K_(bch) capability K_(bch)  5/15 64800 21600 21408 12 192  6/15 2592025728  7/15 30240 30048  8/15 34560 34368  9/15 38880 38688 10/15 4320043008 11/15 47520 47328 12/15 51840 51648 13/15 56160 55968

TABLE 29 BCH error LDPC correction N_(bch)- Rate N_(ldpc) K_(ldpc)K_(bch) capability K_(bch)  5/15 16200 5400 5232 12 168  6/15 6480 6312 7/15 7560 7392  8/15 8640 8472  9/15 9720 9552 10/15 10800 10632 11/1511880 11712 12/15 12960 12792 13/15 14040 13872

The details of operations of the BCH encoding and LDPC encoding are asfollows:

A 12-error correcting BCH code is used for outer encoding of the BBF.The BCH generator polynomial for short FECBLOCK and long FECBLOCK areobtained by multiplying together all polynomials.

LDPC code is used to encode the output of the outer BCH encoding. Togenerate a completed Bldpc (FECBLOCK), Pldpc (parity bits) is encodedsystematically from each Ildpc (BCH-encoded BBF), and appended to Ildpc.The completed Bldpc (FECBLOCK) is expressed as follows.B _(ldpc)=[I _(ldpc) P _(ldpc)]=[i ₀ ,i ₁ , . . . ,i _(K) _(ldpc) ⁻¹ ,p₀ ,p ₁ , . . . ,p _(N) _(ldpc) _(−K) _(ldpc) ⁻¹]  [Expression 3]

The parameters for long FECBLOCK and short FECBLOCK are given in theabove table 28 and 29, respectively.

The detailed procedure to calculate Nldpc−Kldpc parity bits for longFECBLOCK, is as follows:

1) Initialize the parity bits,p ₀ =p ₁ =p ₂ = . . . =p _(N) _(ldpc) _(−K) _(ldpc) ⁻¹=0  [Expression 4]

2) Accumulate the first information bit—i0, at parity bit addressesspecified in the first row of addresses of parity check matrix. Thedetails of addresses of parity check matrix will be described later. Forexample, for rate 13/15:P ₉₈₃ =p ₉₈₃ ⊕i ₀ p ₂₈₁₅ =p ₂₈₁₅ ⊕i ₀ p ₄₈₃₇ =p ₄₈₃₇ ⊕i ₀ p ₄₉₈₉ =p ₄₉₈₉⊕i ₀ p ₆₁₃₈ =p ₆₁₃₈ ⊕i ₀ p ₆₄₅₈ =p ₆₄₅₈ ⊕i ₀ p ₆₉₂₁ =p ₆₉₂₁ ⊕i ₀ p ₆₉₇₄=p ₆₉₇₄ ⊕i ₀ p ₇₅₇₂ =p ₇₅₇₂ ⊕i ₀ p ₈₂₆₀ =p ₈₂₆₀ ⊕i ₀ p ₈₄₉₆ =p ₈₄₉₆ ⊕i₀  [Expression 5]

3) For the next 359 information bits, is, s=1, 2, . . . , 359 accumulateis at parity bit addresses using following expression.{x+(s mod 360)×Q _(ldpc)}mod(N _(ldpc) −K _(ldpc))  [Expression 6]

where x denotes the address of the parity bit accumulator correspondingto the first bit i0, and Qldpc is a code rate dependent constantspecified in the addresses of parity check matrix. Continuing with theexample, Qldpc=24 for rate 13/15, so for information bit i1, thefollowing operations are performed:p ₁₀₀₇ =p ₁₀₀₇ ⊕i ₁ p ₂₈₃₉ =p ₂₈₃₉ ⊕i ₁ p ₄₈₆₁ =p ₄₈₆₁ ⊕i ₁ p ₅₀₁₃ =p₅₀₁₃ ⊕i ₁ p ₆₁₆₂ =p ₆₁₆₂ ⊕i ₁ p ₆₄₈₂ =p ₆₄₈₂ ⊕i ₁ p ₆₉₄₅ =p ₆₉₄₅ ⊕i ₁ p₆₉₉₈ =p ₆₉₉₈ ⊕i ₁ p ₇₅₉₆ =p ₇₅₉₆ ⊕i ₁ p ₈₂₈₄ =p ₈₂₈₄ ⊕i ₁ p ₈₅₂₀ =p ₈₅₂₀⊕i ₁  [Expression 7]

4) For the 361st information bit i360, the addresses of the parity bitaccumulators are given in the second row of the addresses of paritycheck matrix. In a similar manner the addresses of the parity bitaccumulators for the following 359 information bits is, s=361, 362, . .. , 719 are obtained using the expression 6, where x denotes the addressof the parity bit accumulator corresponding to the information bit i360,i.e., the entries in the second row of the addresses of parity checkmatrix.

5) In a similar manner, for every group of 360 new information bits, anew row from addresses of parity check matrixes used to find theaddresses of the parity bit accumulators.

After all of the information bits are exhausted, the final parity bitsare obtained as follows:

6) Sequentially perform the following operations starting with i=1p _(i) =p _(i) ⊕p _(i-) ,i=1,2, . . . ,N _(ldpc) −K _(ldpc)−1  [MathFigure 8]

where final content of pi, i=0, 1, . . . Nldpc−Kldpc−1 is equal to theparity bit pi.

TABLE 30 Code Rate Q_(ldpc)  5/15 120  6/15 108  7/15 96  8/15 84  9/1572 10/15 60 11/15 48 12/15 36 13/15 24

This LDPC encoding procedure for a short FECBLOCK is in accordance witht LDPC encoding procedure for the long FECBLOCK, except replacing thetable 30 with table 31, and replacing the addresses of parity checkmatrix for the long FECBLOCK with the addresses of parity check matrixfor the short FECBLOCK.

TABLE 31 Code Rate Q_(ldpc)  5/15 30  6/15 27  7/15 24  8/15 21  9/15 1810/15 15 11/15 12 12/15 9 13/15 6

FIG. 23 illustrates a bit interleaving according to an embodiment of thepresent invention.

The outputs of the LDPC encoder are bit-interleaved, which consists ofparity interleaving followed by Quasi-Cyclic Block (QCB) interleavingand inner-group interleaving.

It shows Quasi-Cyclic Block (QCB) interleaving and (b) shows inner-groupinterleaving.

The FECBLOCK may be parity interleaved. At the output of the parityinterleaving, the LDPC codeword consists of 180 adjacent QC blocks in along FECBLOCK and 45 adjacent QC blocks in a short FECBLOCK. Each QCblock in either a long or short FECBLOCK consists of 360 bits. Theparity interleaved LDPC codeword is interleaved by QCB interleaving. Theunit of QCB interleaving is a QC block. The QC blocks at the output ofparity interleaving are permutated by QCB interleaving as illustrated inFIG. 23, where Ncells=64800/η mod or 16200/η mod according to theFECBLOCK length. The QCB interleaving pattern is unique to eachcombination of modulation type and LDPC code rate.

After QCB interleaving, inner-group interleaving is performed accordingto modulation type and order (η mod) which is defined in the below table32. The number of QC blocks for one inner-group, NQCB_IG, is alsodefined.

TABLE 32 Modulation type η_(mod) N_(QCB)_IG QAM-16 4 2 NUC-16 4 4 NUQ-646 3 NUC-64 6 6 NUQ-256 8 4 NUC-256 8 8 NUQ-1024 10 5 NUC-1024 10 10

The inner-group interleaving process is performed with NQCB_IG QC blocksof the QCB interleaving output. Inner-group interleaving has a processof writing and reading the bits of the inner-group using 360 columns andNQCB_IG rows. In the write operation, the bits from the QCB interleavingoutput are written row-wise. The read operation is performed column-wiseto read out m bits from each row, where m is equal to 1 for NUC and 2for NUQ.

FIG. 24, including (a) and (b), illustrates a cell-word demultiplexingaccording to an embodiment of the present invention.

FIG. 24(a) shows a cell-word demultiplexing for 8 and 12 bpcu MIMO, andFIG. 24(b) shows a cell-word demultiplexing for 10 bpcu MIMO.

Each cell word (c0,1, c1,1, . . . , cη mod-1,1) of the bit interleavingoutput is demultiplexed into (d1,0,m, d1,1,m . . . , d1,η mod-1,m) and(d2,0,m, d2,1,m . . . , d2,η mod-1,m) as shown in (a), which describesthe cell-word demultiplexing process for one XFECBLOCK.

For the 10 bpcu MIMO case using different types of NUQ for MIMOencoding, the Bit Interleaver for NUQ-1024 is re-used. Each cell word(c0,1, c1,1, . . . , c9,1) of the Bit Interleaver output isdemultiplexed into (d1,0,m, d1,1,m . . . , d1,3,m) and (d2,0,m, d2,1,m .. . , d2,5,m), as shown in (b).

FIG. 25, including (a)-(c), illustrates a time interleaving according toan embodiment of the present invention.

FIG. 25(a) to FIG. 25(c) show examples of TI mode.

The time interleaver operates at the DP level. The parameters of timeinterleaving (TI) may be set differently for each DP.

The following parameters, which appear in part of the PLS2-STAT data,configure the TI:

DP_TI_TYPE (allowed values: 0 or 1): Represents the TI mode; ‘0’indicates the mode with multiple TI blocks (more than one TI block) perTI group. In this case, one TI group is directly mapped to one frame (nointer-frame interleaving). ‘1’ indicates the mode with only one TI blockper TI group. In this case, the TI block may be spread over more thanone frame (inter-frame interleaving).

DP_TI_LENGTH: If DP_TI_TYPE=‘0’, this parameter is the number of TIblocks NTI per TI group. For DP_TI_TYPE=‘1’, this parameter is thenumber of frames PI spread from one TI group.

DP_NUM_BLOCK_MAX (allowed values: 0 to 1023): Represents the maximumnumber of XFECBLOCKs per TI group.

DP_FRAME_INTERVAL (allowed values: 1, 2, 4, 8): Represents the number ofthe frames HUMP between two successive frames carrying the same DP of agiven PHY profile.

DP_TI_BYPASS (allowed values: 0 or 1): If time interleaving is not usedfor a DP, this parameter is set to ‘1’. It is set to ‘0’ if timeinterleaving is used.

Additionally, the parameter DP_NUM_BLOCK from the PLS2-DYN data is usedto represent the number of XFECBLOCKs carried by one TI group of the DP.

When time interleaving is not used for a DP, the following TI group,time interleaving operation, and TI mode are not considered. However,the Delay Compensation block for the dynamic configuration informationfrom the scheduler will still be required. In each DP, the XFECBLOCKsreceived from the SSD/MIMO encoding are grouped into TI groups. That is,each TI group is a set of an integer number of XFECBLOCKs and willcontain a dynamically variable number of XFECBLOCKs. The number ofXFECBLOCKs in the TI group of index n is denoted by NxBLOCK_Group(n) andis signaled as DP_NUM_BLOCK in the PLS2-DYN data. Note thatNxBLOCK_Group(n) may vary from the minimum value of 0 to the maximumvalue NxBLOCK_Group_MAX (corresponding to DP_NUM_BLOCK_MAX) of which thelargest value is 1023.

Each TI group is either mapped directly onto one frame or spread over PIframes. Each TI group is also divided into more than one TI blocks(NTI),where each TI block corresponds to one usage of time interleaver memory.The TI blocks within the TI group may contain slightly different numbersof XFECBLOCKs. If the TI group is divided into multiple TI blocks, it isdirectly mapped to only one frame. There are three options for timeinterleaving (except the extra option of skipping the time interleaving)as shown in the below table 33.

TABLE 33 Modes Descriptions Option- Each TI group contains one TI blockand is mapped directly 1 to one frame as shown in (a). This option issignaled in the PLS2-STAT by DP_TI_TYPE = ‘0’ and DP_TI_ LENGTH =‘1’(N_(TI) = 1). Option- Each TI group contains one TI block and ismapped to more 2 than one frame. (b) shows an example, where one TIgroup is mapped to two frames, i.e., DP_TI_LENGTH = ‘2’ (P_(I) = 2) andDP_FRAME_INTERVAL (I_(JUMP) = 2). This provides greater time diversityfor low data-rate services. This option is signaled in the PLS2-STAT byDP_TI_ TYPE = ‘1’. Option- Each TI group is divided into multiple TIblocks and is 3 mapped directly to one frame as shown in (c). Each TIblock may use full TI memory, so as to provide the maximum bit- rate fora DP. This option is signaled in the PLS2-STAT signaling by DP_TI_TYPE =‘0’ and DP_TI_LENGTH = N_(TI), while P_(I) = 1.

In each DP, the TI memory stores the input XFECBLOCKs (output XFECBLOCKsfrom the SSD/MIMO encoding block). Assume that input XFECBLOCKs aredefined as(d _(n,s,0,0) ,d _(n,s,0,1) , . . . ,d _(n,s,0,N) _(cells) ⁻¹ ,d_(n,s,1,0,) , . . . ,d _(n,s,1,N) _(cells) ⁻¹ , . . . ,d _(n,s,N)_(xBLOCK_TI) _((n,s)-1,0) , . . . ,d _(n,s,N) _(xBLOCK_TI) _((n,s)-1,N)_(cells) ⁻¹),

where d_(n,s,r,q) is the qth cell of the rth XFECBLOCK in the sth TIblock of the nth TI group and represents the outputs of SSD and MIMOencodings as follows

$d_{n,s,r,q} = \left\{ {\begin{matrix}{f_{n,s,r,q},} & {{{the}\mspace{14mu}{output}\mspace{14mu}{of}{\mspace{14mu}\;}{SSD}\mspace{14mu}\ldots\mspace{14mu}{encoding}}\;} \\{g_{n,s,r,q},} & {{the}\mspace{14mu}{output}\mspace{14mu}{of}{\mspace{14mu}\;}{MIMO}\mspace{14mu}{encoding}}\end{matrix}.} \right.$

In addition, assume that output XFECBLOCKs from the time interleaver5050 are defined as(h _(n,s,0) ,h _(n,s,1) , . . . ,h _(n,s,i) , . . . ,h _(n,s,N)_(xBLOCK_TI) _((n,s)×N) _(cells) ⁻¹),

where h_(n,s,i) is the ith output cell (for i=0, . . . ,N_(xBLOCK_TI)(n,s)×N_(cells)−1) in the sth TI block of the nth TI group.

Typically, the time interleaver will also act as a buffer for DP dataprior to the process of frame building. This is achieved by means of twomemory banks for each DP. The first TI-block is written to the firstbank. The second TI-block is written to the second bank while the firstbank is being read from and so on.

The TI is a twisted row-column block interleaver. For the sth TI blockof the nth TI group, the number of rows N_(r) of a TI memory is equal tothe number of cells N_(cells), i.e., N_(r)=N_(cells) while the number ofcolumns N_(c) is equal to the number N_(xBLOCK_TI)(n,s).

FIG. 26, including (a) and (b), illustrates the basic operation of atwisted row-column block interleaver according to an embodiment of thepresent invention.

FIG. 26(a) shows a writing operation in the time interleaver and FIG.26(b) shows a reading operation in the time interleaver. The firstXFECBLOCK is written column-wise into the first column of the TI memory,and the second XFECBLOCK is written into the next column, and so on asshown in FIG. 26(a). Then, in the interleaving array, cells are read outdiagonal-wise. During diagonal-wise reading from the first row(rightwards along the row beginning with the left-most column) to thelast row, N_(r) cells are read out as shown in (b). In detail, assumingz_(n,s,i)(i=0, . . . , N_(r)N_(c)) as the TI memory cell position to beread sequentially, the reading process in such an interleaving array isperformed by calculating the row index R_(n,s,i), the column indexC_(n,s,i), and the associated twisting parameter T_(n,s,i) as followsexpression.

$\begin{matrix}{{{GENERATE}\mspace{11mu}\left( {R_{n,s,i},C_{n,s,i}} \right)} = \left\{ {{R_{n,s,i} = {{mod}\mspace{11mu}\left( {i,N_{r}} \right)}},{T_{n,s,i} = {{mod}\mspace{11mu}\left( {{S_{shift} \times R_{n,s,i}},N_{c}} \right)}},{C_{n,s,i} = {{mod}\mspace{11mu}\left( {{T_{n,s,i} + \left\lfloor \frac{i}{N_{r}} \right\rfloor},N_{c}} \right)}}} \right\}} & \left\lbrack {{Expression}\mspace{14mu} 9} \right\rbrack\end{matrix}$

where S_(shift) is a common shift value for the diagonal-wise readingprocess regardless of N_(xBLOCK_TI)(n,s), and it is determined byN_(xBLOCK_TI_MAX) given in the PLS2-STAT as follows expression.

$\begin{matrix}{{f{or}}\left\{ {\begin{matrix}{{N_{{{xBLOCK}\_{TI}}{\_{MAX}}}^{\prime} = {N_{{{xBLOCK}\_{TI}}{\_{MAX}}} + 1}},} & {{{if}\mspace{14mu} N_{{{xBLOCK}\_{TI}}{\_{MAX}}}\;{mod}\mspace{11mu} 2} = 0} \\{{N_{{xBLOCK}\mspace{11mu}{TI}\mspace{11mu}{MAX}}^{\prime} = N_{{xBLOCK}\mspace{11mu}{TI}\mspace{11mu}{MAX}}},} & {{{if}{\;\mspace{11mu}}N_{{xBLOCK}\mspace{11mu}{TI}\mspace{11mu}{MAX}}\;{mod}\mspace{11mu} 2} = 1}\end{matrix},{S_{shift} = \frac{N_{{{xBLOCK}\_{TI}}{\_{MAX}}}^{\prime} - 1}{2}}} \right.} & \left\lbrack {{Expression}\mspace{14mu} 10} \right\rbrack\end{matrix}$

As a result, the cell positions to be read are calculated by acoordinate as z_(n,s,i)=N_(r)C_(n,s,i)+R_(n,s,i).

FIG. 27 illustrates an operation of a twisted row-column blockinterleaver according to another embodiment of the present invention.

More specifically, FIG. 27 illustrates the interleaving array in the TImemory for each TI group, including virtual XFECBLOCKs whenN_(xBLOCK_TI)(0,0)=3, N_(xBLOCK_TI)(1,0)=6, N_(xBLOCK_TI)(2,0)=5.

The variable number N_(xBLOCK_TI)(n,s)=N_(r) will be less than or equalto N′_(xBLOCK_TI_MAX). Thus, in order to achieve a single-memorydeinterleaving at the receiver side, regardless of N_(xBLOCK_TI)(n,s),the interleaving array for use in a twisted row-column block interleaveris set to the size of N_(r)×N_(c)=N_(cells)×N_(xBLOCK_TI_MAX) byinserting the virtual XFECBLOCKs into the TI memory and the readingprocess is accomplished as follow expression.

(Expression 11)   p = 0; for i = 0;i < N_(cells)N′_(xBLOCK)_TI_MAX;i =i + 1 {GENERATE (R_(n,s,i), C_(n,s,i)); V_(i) = N_(r)C_(n,s,j) +R_(n,s,j)  if V_(i) < N_(cells)N_(XBLOCK)_TI(n,s)  {   Z_(n,s,p) =V_(i); p = p + 1;   } }

The number of TI groups is set to 3. The option of time interleaver issignaled in the PLS2-STAT data by DP_TI_TYPE=‘0’, DP_FRAME_INTERVAL=‘1’,and DP_TI_LENGTH=‘1’, i.e., NTI=1, IJUMP=1, and PI=1. The number ofXFECBLOCKs, each of which has Ncells=30 cells, per TI group is signaledin the PLS2-DYN data by NxBLOCK_TI(0,0)=3, NxBLOCK_TI(1,0)=6, andNxBLOCK_TI(2,0)=5, respectively. The maximum number of XFECBLOCK issignaled in the PLS2-STAT data by NxBLOCK_Group_MAX, which leads to└N_(xBLOCK_Group_MAX)/N_(TI)┘=N_(xBLOCK_TI_MAX)=6.

FIG. 28 illustrates a diagonal-wise reading pattern of a twistedrow-column block interleaver according to an embodiment of the presentinvention.

More specifically FIG. 28 shows a diagonal-wise reading pattern fromeach interleaving array with parameters of N′_(xBLOCK_TI_MAX)=7 andSshift=(7−1)/2=3. Note that in the reading process shown as pseudocodeabove, if V_(i)≥N_(cells)N_(xBLOCK_TI)(n,s), the value of Vi is skippedand the next calculated value of Vi is used.

FIG. 29 illustrates interleaved XFECBLOCKs from each interleaving arrayaccording to an embodiment of the present invention.

FIG. 29 illustrates the interleaved XFECBLOCKs from each interleavingarray with parameters of N′_(xBLOCK_TI_MAX)=7 and Sshift=3.

The frequency interleaving process according to one embodiment of thepresent invention will hereinafter be described.

The frequency interleaver 7020 according to one embodiment is configuredto apply different interleaving sequences to respective cellscorresponding to each OFDM symbol so as to improve the frequencydiversity performance in the OFDM symbol structure composed of aplurality of cells.

In the present invention, the above-mentioned frequency interleavingmethod may be referred to as ‘random frequency interleaving’ or ‘randomFI’, and may also be changed according to designer's intention.

The above-mentioned broadcast signal transmission apparatus or thefrequency interleaver 7020 contained in the broadcast signaltransmission apparatus may apply different interleaving sequences eitherto constituent symbols (i.e., respective symbols) of at least one frameor to respective cells corresponding to two paired symbols, and mayperform frequency interleaving, thereby obtaining the frequencydiversity.

The at least one symbol may be converted into at least one OFDM symbolsin a subsequent modulation process. That is, the at least one symbol maybe converted into each OFDM symbol or two paired OFDM symbols (i.e.,pair-wise OFDM symbol or each OFDM symbol pair).

The frequency interleaver according to one embodiment may performfrequency interleaving of cells corresponding to OFDM symbols enteredusing the frequency interleaving address generated on the basis of themain interleaving sequence (or basic interleaving sequence) and thesymbol offset.

Hereinafter, a description will be given of MIMO processing (or a MIMOencoding method or decoding method) according to an embodiment of thepresent invention.

A next generation broadcast system according to an embodiment of thepresent invention may use a MIMO scheme to deliver more data. Inparticular, the next generation broadcast system according to thepresent embodiment may overcome a correlated channel environment inwhich channel capacity is decreased and system operation is disturbedusing dual-polar MIMO in which a signal is transmitted using avertical/horizontal polarity of an antenna. However, even whendual-polar MIMO is used, two components may have different power ratiosaccording to difference in radio wave propagation characteristic of avertical/horizontal polarity. In other words, a power imbalance statemay occur. In this state, power is different between a signal outputfrom an antenna of a horizontal polarity and a signal output from anantenna of a vertical polarity. To overcome this power imbalanceenvironment, the MIMO scheme according to the present embodiment mayinclude a PH-eSM scheme (PH-eSM PI) that requires less complexity of areceiver, a full-rate full-diversity (FRFD) scheme (FRFD PH-eSM PI) thatcan exhibit higher performance even though a design of the receiver iscomplex, and a scheme created by combining each of the above schemeswith a non-uniform constellation (NUC). The PH-eSM scheme refers to ascheme of rotating angles of signals input to a MIMO decoder to overcomecomplexity of the receiver and power imbalance. The FRFD scheme is ascheme of acquiring additional diversity gain in the frequency domain byadding additional complexity.

When MIMO is combined with an NUC, the NUC uses a grid value optimizedfor each SNR (or code rate of FEC or combination of modulation and coderate (MODCOD)). Thus, when MIMO encoding is performed, a transmittingend needs to use a parameter “a” of MIMO encoding having an optimizedvalue for each SNR.

Hereinafter, a scheme will be proposed to optimize the MIMO parameter“a” according to SNR or MODCOD in a MIMO system to which an NUC (1D-NUCor 2D-NUC) is applied. In addition, a description will be given of amethod of reducing complexity of the receiver using a decoder suitablefor an NUC (for example, a sphere decoder (SD) and a complex-spheredecoder).

FIG. 30, including (a) and (b), shows equations that express a matrixaccording to the MIMO scheme according to an embodiment of the presentinvention.

Specifically, FIG. 30(a) is an equation that expresses the PH-eSM schemeor a MIMO matrix according to the PH-eSM scheme, and FIG. 30(b) is anequation that expresses the FRFD scheme or a MIMO matrix according tothe FRFD scheme.

As described in the foregoing, the PH-eSM scheme is a scheme thatreduces complexity according to MIMO decoding. A MIMO processor maygenerate signals Xi and X₂ to be transmitted using two transmittedsymbols (input symbols or a symbol pair) output from a constellationmapper, for example, QAM symbols S₁ and S₂. In an OFDMtransmission/reception system, the signals X₁ and X₂ may be transmittedon the same frequency carrier f₁ (X₁(f₁), X₂(f₁)). Here, the signal X₁may be transmitted through an antenna 1 (TX1), and the signal X₂ may betransmitted through an antenna 2 (TX2). According to this scheme, evenwhen power imbalance is present between two transmit antennas, it ispossible to implement efficient signal transmission that minimizes loss.

In a left part of the figure, a value X refers to an output of MIMOprocessing of a transmitter, S refers to an input signal, and P refersto a MIMO matrix. P may be referred to as a precoding matrix.

The precoding matrix may include a rotation matrix for combiningconstellations of input symbols by rotating angles of the input symbols,and a phase-hopping matrix for configuring phase rotation of symbolstransmitted through the antenna 2 (TX2).

“a” in the rotation matrix may be referred to as a MIMO parameter. Wheninput symbols correspond to QAM symbols, a value thereof may bedetermined according to QAM order. When the receiver receives thesignals X₁ and X₂ and independently decodes the signals X₁ and X₂, thatis, when the receiver decodes the symbols S₁ and S₂ only using thesignal X₁ or decodes the symbols S₁ and S₂ only using the signal X₂, avalue of “a” is optimized based on Euclidean distance and Hammingdistance. Thus, the receiver may obtain low bit error rate (BER)performance. The receiver according to the present embodiment mayperform ML and sub-ML (sphere) decoding, etc. using the matrix shown inthe figure to perform a reverse operation of MIMO processing at atransmitting side.

A parameter 0 of the phase-hopping matrix indicates a phase rotationangle, and a value thereof is determined according to the equation shownin the figure.

The FRFD scheme is a scheme of obtaining high performance by performingmore complex decoding in the receiver.

As illustrated in the figure, the MIMO processor on the transmittingside may receive four input symbols S₁, S₂, S₃, and S₄ and outputtransmitted signals X₁ and X₂ using the matrix shown in the figure. Inthis case, the same value as a parameter according to the PH-eSM schememay be used as the MIMO parameter a.

In addition, in the FRFD scheme, the output signals X₁ and X₂ may betransmitted on two frequency carriers f₁ and f₂ (X₁(f₁), X₂(f₁), X₁(f₂),X₂(f₂)). Therefore, the signal X₁ is transmitted through two frequencycarriers of the antenna 1 (TX1), and the signal X₂ is transmittedthrough two frequency carriers of the antenna 2 (TX2). Thus, this schemehas an advantage of effectively coping with a case in which powerimbalance occurs between carriers in addition to power imbalance betweenantennas.

FIG. 31, including (a) and (b), shows the MIMO parameter “a” when an NUCis applied according to an embodiment of the present invention.

The above-described MIMO parameter “a” may have a different valueaccording to uniform QAM and 1D-NUC modulation value of an input symbol.

FIG. 31(a) shows examples of a value of the MIMO parameter “a” accordingto QAM combinations, and FIG. 31(b) shows a process of determining thevalue of the MIMO parameter “a” according to 1D-NUC modulation and thevalue a according to each modulation combination.

As shown in FIG. 31(a), the value of the MIMO parameter “a” may be setaccording to QAM combinations, that is, QPSK, 16 QAM, 64 QAM, and 256QAM.

In addition, as shown in FIG. 31(b), in a 1D-NUC modulation combination,the value of the MIMO parameter “a” may be calculated by defining a PAMgrid of a used I or Q component and using a largest value (Pm) and asecond largest value (Pm−1) of the grid. Therefore, the receiver mayseparately decode a signal received through one antenna by applying thevalue a.

Further, as shown in the figure, the value a may be calculated using asub-constellation separation factor b. The factor b refers to aparameter for adjusting an interval between sub-constellations presentin a MIMO-processed signal. In an example of the present invention, thefactor b has a value of

$\frac{\sqrt{2}}{2}.$The value b refers to a value obtained by adjusting a Euclidean distanceand a Hamming distance based on a point having largest power and anadjacent point thereof in constellations.

However, in 1D-NUC, a grid value optimized for each code rate of 1-EC orSNR is used, and thus the MIMO parameter “a” needs to have an optimizedvalue for each SNR.

Therefore, the present invention proposes a method of calculating avalue of the MIMO parameter “a” optimized for each SNR. To apply an NUCto the above-described two MIMO schemes for each SNR (or FEC code rate),the following two factors need to be considered.

First, an NUC, which is most suitable for MIMO, needs to be found toobtain shaping gain. Second, a value of the MIMO parameter “a” needs tobe calculated in an NUC optimized for each SNR.

However, when an NUC suitable for each SNR and the MIMO parameter “a”are simultaneously calculated through capacity analysis of BICM in aMIMO environment, the calculation may be restricted due to operationquantity. Therefore, the present invention proposes the followingprocess.

First, an NUC suitable for MIMO is determined by comparing performancesof NUCs optimized for SISO on a non-power imbalanced MIMO channel foreach SNR (or FEC code rate). When a BICM capacity can be analyzed on aMIMO channel, it is possible to obtain an optimized NUC for MIMO whichprovides a maximum capacity at a certain SNR by analyzing capacitiesaccording to SNRs.

However, when operation quantity is too large to perform actualcalculation, an NUC for MIMO may be determined by comparing performancesusing an optimized NUC set (NUC for each SNR) in SISO. For example, anNUC for MIMO at a code rate of 5/15 of 12 bpcu (1D-64NUC+1D-64NUC) maybe determined to be 1D-64NUC corresponding to an SISO code rate of 5/15.

Thereafter, a MIMO parameter “a” optimized for each SNR may becalculated by analyzing capacities in a power imbalanced MIMO channelenvironment based on an NUC determined through the above-describedprocess.

FIG. 32, including (a) and (b), shows an equation that expresses a MIMOscheme in consideration of power imbalance and a correlated channelenvironment and an equation that expresses a capacity of BICM accordingto an embodiment of the present invention.

Specifically, FIG. 32(a) shows an equation that expresses a MIMO schemein consideration of power imbalance and a correlated channelenvironment, and FIG. 32(b) shows an equation that expresses a capacityof BICM.

As shown in FIG. 32(a), according to an embodiment of the presentinvention, a power imbalance (PI) factor α and an active white Gaussiannoise (AWGN) value are applied to the above-described MIMO matrix inorder to consider a correlated channel environment and a power imbalancechannel environment which can be generated when the MIMO scheme is used.The factor α according to the present embodiment may have values asbelow according to magnitudes of PI.

PI 9 dB: 0.354817, PI 6 dB: 0.501187, PI 3 dB: 0.70711

In addition, as shown in FIG. 32(b), a BICM capacity may be determinedon the assumption of AWGN and individually identically distributed (IID)input.

In other words, an algorithm for obtaining a value of the parameter aproposed in the present invention is as below.

First step: An initial NUC of an SNR or a MIMO FEC code rate (CR) havingoptimum performance is obtained by comparing BER performance using anNUC corresponding to an FEC code rate (5/15, 6/15, 7/15, . . . , 13/15)of SISO. For example, an NUC of a MIMO FEC CR of 6/15 may have an NUCcorresponding to an SISO FEC CR of 5/15.

Second step: A MIMO parameter “a” having optimum performance may becalculated by analyzing BICM performance as described above withreference to FIG. 32 with respect to the NUC obtained in the first step.In this case, a value of the parameter a may be calculated based on apower imbalance and a correlated channel environment described abovewith reference to FIG. 32.

FIG. 33, including (a) and (b), shows an equation that expresses acondition of a MIMO decoder for an NUC.

A receiver according to an embodiment of the present invention mayperform a reverse operation of MIMO processing on the transmitting side.In addition, this figure illustrates a MIMO decoder for reducingcomplexity in a MIMO system to which an NUC is applied.

An SD refers to a MIMO decoder having reduced complexity while havingmaximum-likelihood (ML) performance Therefore, the MIMO decoderaccording to the present embodiment may find a constellation point freeof noise within a radius R of a hyper-sphere around a received signal r.The equation shown in FIG. 33(a) expresses ML according to a relationamong the received signal r, the constellation point free of noise, andthe radius R of the hyper-sphere, and FIG. 33(b) illustratesconstellation points free of noise within the value of R of thehyper-sphere around the received signal. In the equation, HS denotes theconstellation point free of noise.

Most SDs are based on a real-valued SD which is based on a constellationbased on QAM or PSK. However, these SDs are not suitable for applicationto an NUC such as 2D-NUC. Therefore, an embodiment of the presentinvention may be based on a complex SD suitable for 2D-NUC. The complexSD suitable for 2D-NUC is advantageous in optimizing hardware execution.Thus, a value of an initial radius R may be selected according to changein noise for each antenna, and complexity of an algorithm may be basedon a noise level and a channel condition. In other words, according toan embodiment of the present invention, a broadcast signaltransmission/reception system may use a value of R according to aconstellation of each MODCOD to optimize MIMO performance

FIG. 34 shows MIMO constellations and MIMO parameters “a” proposed for 8bpcu, 12 bpcu, and 16 bpcu according to an embodiment of the presentinvention.

A leftmost column of a table shown in the figure indicates code rates,and an upper row of the table indicates values of bpcu.

When a constellation according to an embodiment of the present inventionis used, it is possible to obtain shaping gain optimized for each coderate (MODCOD). In addition, a MIMO parameter “a” according to thepresent embodiment may optimize MIMO performance when a constellationoptimized for each MODCOD is applied. Further, optimum performance foreach MODCOD may be acquired by applying a constellation and a MIMOparameter “a” according to the present embodiment.

FIG. 35 shows MIMO constellations and MIMO parameters “a” proposed for 8bpcu, 12 bpcu, and 16 bpcu according to another embodiment of thepresent invention.

This figure shows a constellation that optimizes performance whilemaintaining a baseline of SISO for a constellation acquired through theabove-described method for 8 bpcu, 12 bpcu, and 16 bpcu.

A leftmost column of a table shown in the figure indicates code rates,and an upper row of the table indicates values of bpcu. A MIMO parameter“a” is a value that can optimize MIMO performance when a constellationoptimized for each MODCOD is applied.

When the constellation according to the embodiment of the presentinvention is used, it is possible to obtain optimized shaping gain whilemaintaining a baseline of SISO for each code rate (MODCOD) as much aspossible. Therefore, additional configurations for MIMO may be reducedin the transmitter and the receiver, and thus complexity of atransmission/reception configuration may be reduced. In addition, it ispossible to obtain optimum performance for each MODCOD by applying theconstellation and the MIMO parameter “a” according to the presentembodiment.

FIG. 36 shows MIMO constellations and MIMO parameters “a” proposed for20 bpcu and 24 bpcu according to an embodiment of the present invention.

The present embodiment is different from the embodiments described abovewith reference to FIGS. 34 and 35 in values of bpcu, and details thereofare the same. Thus, a description of the details will be omitted.

FIG. 37 shows a type of a precoding matrix of the PH-eSM schemeaccording to an embodiment of the present invention.

An equation shown at the top of the figure expresses a MIMO matrix ofthe above-described PH-eSM scheme, and four types of precoding matricesin the equation shown at the top of the figure are shown at the bottomof the figure.

As described in the foregoing, the MIMO matrix of the PH-eSM scheme mayinclude a precoding matrix (P), and the precoding matrix may include arotation matrix and a phase rotation matrix. The rotation matrix mayinclude the above-described MIMO parameter “a”, and the rotation matrixmay be expressed in the four types as shown at the bottom of the figure.

The four types of precoding matrices shown at the bottom of the figureare different from one another only in terms of expression and aresubstantially the same. That is, the MIMO parameter “a” may be expressedusing a rotation angle θ.

In the precoding matrix of Type 4, a value of the matrix may be changedaccording to a value of n without fixing a rotation angle of a rotationmatrix used for precoding. In this case, the value of n may changeaccording to an OFDM carrier index or change according to an OFDM symbolindex. The receiver may decode the value of n in synchronization withthe transmitter. Therefore, when the precoding matrix of Type 4 is used,there is an advantage of obtaining average performance of severalrotation angles without being affected by MIMO encoding performancewhich depends on a particular rotation angle of a rotation matrix.

In this case, a value of “a” and a value of a rotation angle may bedetermined based on a constellation value. When the signals X₁ and X₂respectively transmitted through the antenna 1 (TX1) and the antenna 2(TX2) are independently decoded, that is, when the symbols S₁ and S₂ aredecoded only using the signal X₁ or only using the signal X₂, a value of“a” is optimized based on Euclidean distance and Hamming distance. Thus,the receiver may obtain low BER performance

The receiver may perform ML and sub-ML (sphere) decoding, etc. using thematrix shown in the figure on signals MIMO-processed using the matrix,thereby performing a reverse operation of MIMO processing on thetransmitting side.

FIG. 38 shows a MIMO matrix of the FRFD scheme according to anembodiment of the present invention.

As described in the foregoing, the FRFD scheme is a scheme of obtaininghigh performance by performing more complex decoding in the receiver.Details are the same as the above description with reference to FIG. 30.Four types of matrices shown in the figure are different from oneanother only in terms of expression and are substantially the same.

FIG. 39 shows signaling information for signaling a MIMO matrixaccording to an embodiment of the present invention.

The present invention proposes a method of transmitting a value of aMIMO parameter “a” using a signaling field (or signaling information)for signaling the value to the receiver. The signaling field may beexpressed by MIMO encoding_parameter, and have a size of 4 bits. Inaddition, a bit resolution of a MIMO parameter may vary according tosize of the signaling field.

The signaling field according to the present embodiment may be includedin PLS1 or PLS2 described above. In addition, PLS1 and PLS2 according tothe present embodiment may be referred to as L1 signaling information.The receiver according to the present embodiment may receive theabove-described signaling information to perform flexible decoding.

A signaling field indicating a MIMO parameter (or MIMO encodingparameter) of a matrix corresponding to Type 2 is shown on the left sideof the figure, and a signaling field indicating a MIMO parameter (orMIMO encoding parameter) of a matrix corresponding to Type 3 is shown onthe right side of the figure.

Each of the MIMO parameter of the matrix corresponding to Type 2 and theMIMO parameter of the matrix corresponding to Type 3 may be defined as“a” or a rotation angle. A relation between the two parameters is shownat the bottom of the figure.

Therefore, in Type 2, “a” corresponds to 0 when a value of MIMOencoding_parameter corresponds to 0, and “a” corresponds to 1 when avalue of MIMO encoding_parameter corresponds to 9. In a similar manner,in Type 3, a rotation angle corresponds to 0° when a value of MIMOencoding_parameter corresponds to 0, and a rotation angle corresponds to45° when a value of MIMO encoding_parameter corresponds to 9.

In addition, a bit resolution of a MIMO parameter according to a valueof MIMO encoding_parameter may change. Further, in Type 3, a resolutionbetween MIMO parameters determined according to a value of MIMOencoding_parameter based on 4 bits may correspond to 5 degrees.

MIMO parameters of matrices corresponding to Type 1 and Type 4 accordingto an embodiment of the present invention may have similar values tothose of MIMO parameters of matrices corresponding to Type 2 and Type 3.

FIG. 40 shows MIMO constellations and MIMO parameters proposed for 4bpcu and 8 bpcu according to another embodiment of the presentinvention.

FIG. 40 shows optimized MIMO parameters when an ML decoder is applied to4 bpcu (QPSK+QPSK) and 8 bpcu (16NUC+16NUC).

FIG. 40 shows rotation angles as another embodiment of the MIMOparameters described above with reference to FIGS. 34 to 36. Inaddition, a rotation angle may be expressed using “a” according to anequation shown at the right top of the table.

A leftmost column of the table shown in the figure indicates code rates,and an upper row of the table indicates values of bpcu.

When the receiver performs ML decoding, optimum MIMO performance may beobtained by applying the MIMO parameters shown in the figure.

A MIMO parameter rotation angle according to an embodiment of thepresent invention may optimize MIMO performance when a constellationoptimized for each MODCOD is applied. In addition, optimum performancemay be obtained for each MODCOD by applying a constellation and a MIMOparameter rotation angle according to the present embodiment.

FIG. 41 shows MIMO constellations and MIMO parameters proposed for 12bpcu, 16 bpcu and 20 bpcu according to another embodiment of the presentinvention.

FIG. 41 shows optimized MIMO parameters when a linear receiver isapplied to 12 bpcu (64NUC+64NUC), 16 bpcu (256NUC+256NUC), and 20 bpcu(1024NUC+1024NUC).

The linear receiver according to the present embodiment may include aMIMO demapper using an equalizer based on an MMSE filter. In this case,optimum MIMO performance may be obtained when the MIMO parameters shownin the figure are used. When the MIMO parameters and a lineartype-reception configuration are used, there is an advantage of reducingcomplexity of the receiver while minimizing performance deterioration.

A MIMO parameter rotation angle according to an embodiment of thepresent invention may optimize MIMO performance when a constellationoptimized for each MODCOD is applied. In addition, optimum performancemay be obtained for each MODCOD by applying a constellation and a MIMOparameter rotation angle according to the present embodiment.

FIG. 42 shows MIMO constellations and MIMO parameters proposed for 24bpcu according to another embodiment of the present invention.

FIG. 42 shows optimized MIMO parameters when a linear receiver isapplied to 24 bpcu (2048NUC+2048NUC). The present embodiment isdifferent from the embodiment described above with reference to FIG. 41in values of bpcu, and details thereof are the same. Thus, the detailswill be omitted.

FIG. 43 is a flowchart illustrating a method for receiving broadcastsignals according to an embodiment of the present invention.

The apparatus for receiving broadcast signals according to an embodimentof the present invention may perform a reverse process of transmittingbroadcast signals which is described in FIG. 1 to FIG. 8, FIG. 10 toFIG. 57.

The apparatus for receiving broadcast signals according to an embodimentof the present invention or a receiver can receive broadcast signals(S43000).

Then the apparatus for receiving broadcast signals according to anembodiment of the present invention or a synchronization & demodulationmodule in the apparatus for receiving broadcast signals can demodulatethe received broadcast signals by an OFDM (Orthogonal Frequency DivisionMultiplexing) scheme (S43100). Details are as described in FIG. 9.

The apparatus for receiving broadcast signals according to an embodimentof the present invention or the frame parsing module can parse at leastone signal frame from the frequency deinterleaved broadcast signals(S43200). The detailed process of parsing is as described in FIG. 9.

Then the apparatus for receiving broadcast signals according to anembodiment of the present invention or the demapping & decoding modulein the apparatus for receiving broadcast signals can MIMO processservice data in the parsed signal frame (S43300). More specifically, theMIMO processing of an apparatus for transmitting broadcast signals isperformed on a pair of symbols of the mapped service data based on arotation matrix with a rotation angle. The value of the rotation angledepends on a modulation order and code rate of the service data and themodulation order is one of QPSK modulation and NUC (non-uniformconstellation). The details of MIMO processing are as described in FIG.30 to FIG. 42. The apparatus for receiving broadcast signals accordingto an embodiment of the present invention can perfume MIMO processing asa reverse process of the apparatus for transmitting.

Then, the apparatus for receiving broadcast signals according to anembodiment of the present invention or the demapping & decoding modulecan de-map the MIMO processed service data (S43400) and decode thedemapped service data (S43500). The detailed process of the two steps isas described in FIG. 9.

It will be appreciated by those skilled in the art that variousmodifications and variations can be made in the present inventionwithout departing from the spirit or scope of the inventions. Thus, itis intended that the present invention covers the modifications andvariations of this invention provided they come within the scope of theappended claims and their equivalents.

Both apparatus and method inventions are mentioned in this specificationand descriptions of both of the apparatus and method inventions may becomplementarily applicable to each other.

A module, a unit or a block according to embodiments of the presentinvention is a processor/hardware executing a sequence of instructionsstored in a memory (or storage unit). The steps or the methods in theabove described embodiments can be operated in/by hardwares/processors.In addition, the method of the present invention may be implemented as acode that may be written on a processor readable recording medium andthus, read by the processors provided in the apparatus according toembodiments of the present invention.

What is claimed is:
 1. A method for processing broadcast signals, themethod comprising: receiving the broadcast signals carrying servicedata; demodulating the broadcast signals by an Orthogonal FrequencyDivision Multiplexing (OFDM) scheme; Multiple Input Multiple Output(MIMO) processing data in the broadcast signals based on a rotationvalue, the rotation value has zero (0) degree for a modulation ordercorresponding to equal to or greater than 64 Quadrature AmplitudeModulation (QAM) and a code rate corresponding to at least one of 2/15,3/15, 4/15, 5/15, 6/15, 7/15, 8/15, 9/15, 10/15, 11/15, 12/15 or 13/15,the rotation value has zero (0) degree for a modulation ordercorresponding to Quadrature Phase Shift Keying (QPSK) and a code ratecorresponding to at least one of 2/15, 3/15, 4/15 or 5/15, the rotationvalue has non-zero degree for a modulation order corresponding toQuadrature Phase Shift Keying (QPSK) and a code rate corresponding to atleast one of 6/15, 7/15, 8/15, 9/15, 10/15, 11/15, 12/15 or 13/15; anddecoding the data.
 2. The method of claim 1, wherein the data in theMIMO processing is rotated based on a matrix having the rotation value.3. A device for processing broadcast signals, the device comprising: atuner configured to receive the broadcast signals carrying service data;a demodulator configured to demodulate the broadcast signals by anOrthogonal Frequency Division Multiplexing (OFDM) scheme; a MultipleInput Multiple Output (MIMO) processor configured to MIMO process datain the broadcast signals based on a rotation value, the rotation valuehas zero (0) degree for a modulation order corresponding to equal to orgreater than 64 Quadrature Amplitude Modulation (QAM) and a code ratecorresponding to at least one of 2/15, 3/15, 4/15, 5/15, 6/15, 7/15,8/15, 9/15, 10/15, 11/15, 12/15 or 13/15, the rotation value has zero(0) degree for a modulation order corresponding to Quadrature PhaseShift Keying (QPSK) and a code rate corresponding to at least one of2/15, 3/15, 4/15 or 5/15, the rotation value has non-zero degree for amodulation order corresponding to Quadrature Phase Shift Keying (QPSK)and a code rate corresponding to at least one of 6/15, 7/15, 8/15, 9/15,10/15, 11/15, 12/15 or 13/15; and a decoder configured to decode thedata.
 4. The device of claim 3, wherein the data, by the MIMO processor,is rotated based on a matrix having the rotation value.
 5. A method fortransmitting broadcast signals, the method comprising: encoding data;Multiple Input Multiple Output (MIMO) processing the data based on arotation value, the rotation value has zero (0) degree for a modulationorder corresponding to equal to or greater than 64 Quadrature AmplitudeModulation (QAM) and a code rate corresponding to at least one of 2/15,3/15, 4/15, 5/15, 6/15, 7/15, 8/15, 9/15, 10/15, 11/15, 12/15 or 13/15,the rotation value has zero (0) degree for a modulation ordercorresponding to Quadrature Phase Shift Keying (QPSK) and a code ratecorresponding to at least one of 2/15, 3/15, 4/15 or 5/15, the rotationvalue has non-zero degree for a modulation order corresponding toQuadrature Phase Shift Keying (QPSK) and a code rate corresponding to atleast one of 6/15, 7/15, 8/15, 9/15, 10/15, 11/15, 12/15 or 13/15;modulating broadcast signals including the data by an OrthogonalFrequency Division Multiplexing (OFDM) scheme; and transmitting thebroadcast signals.
 6. An apparatus for transmitting broadcast signals,the apparatus comprising: an encoder configured to encode data; aMultiple Input Multiple Output (MIMO) processor configured to MIMOprocess the data based on a rotation value, the rotation value has zero(0) degree for a modulation order corresponding to equal to or greaterthan 64 Quadrature Amplitude Modulation (QAM) and a code ratecorresponding to at least one of 2/15, 3/15, 4/15, 5/15, 6/15, 7/15,8/15, 9/15, 10/15, 11/15, 12/15 or 13/15, the rotation value has zero(0) degree for a modulation order corresponding to Quadrature PhaseShift Keying (QPSK) and a code rate corresponding to at least one of2/15, 3/15, 4/15 or 5/15, the rotation value has non-zero degree for amodulation order corresponding to Quadrature Phase Shift Keying (QPSK)and a code rate corresponding to at least one of 6/15, 7/15, 8/15, 9/15,10/15, 11/15, 12/15 or 13/15; a modulator configured to modulatebroadcast signals including the data by an Orthogonal Frequency DivisionMultiplexing (OFDM) scheme; and a transmitter configured to transmit thebroadcast signals.